Regarding the change of names mentioned in the document, such as Hitachi
Electric and Hitachi XX, to Renesas Technology Corp.
The semiconductor operations of Mitsubishi Electric and Hitachi were transferred to Renesas
Technology Corporation on April 1st 2003. These operations include microcomputer, logic, analog
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Accordingly, although Hitachi, Hitachi, Ltd., Hitachi Semiconductors, and other Hitachi brand
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Technology Corp. Thank you for your understanding. Except for our corporate trademark, logo and
corporate statement, no changes whatsoever have been made to the contents of the document, and
these changes do not constitute any alteration to the contents of the document itself.
Renesas Technology Home Page: http://www.renesas.com
Renesas Technology Corp.
Customer Support Dept.
April 1, 2003
To all our customers
Cautions
Keep safety first in your circuit designs!
1. Renesas Technology Corporation puts the maximum effort into making semiconductor products better
and more reliable, but th ere is always the possibility that trouble may occur with them. Trouble with
semiconductors may lead to personal injury, fire or property damage.
Remember to give due consideration to safety when making your circuit designs, with appropriate
measures such as (i) placement of substitutive, auxiliary circuits, (ii) use of nonflammable material or
(iii) prevention against any malfunction or mishap.
Notes regar ding these materials
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contained therein.
HA17384SPS/SRP, HA17384HPS/HRP,
HA17385HPS/HRP
High Speed Current Mode PWM Control IC
for Switching Power Supply
ADE-204-028B (Z)
Rev.2
Jul. 2002
Description
The HA17384S/H and HA17385H are PWM control switching regulator IC series suitable for highspeed,
current-mode switching power supplies. With ICs from this series and a few external parts, a small, low
cost flyback-transformer switching power supply can be constructed, which facilitates good line regulation
by current mode control. Synchronous operation driven after an external signal can also be easily obtained
which offers various applications such as a power supply for monitors small multi-output power supply.
The IC series are composed of circuits required for a switching regulator IC. That is a under-voltage
lockout (UVL), a high precision reference voltage regulator (5.0 V ± 2%), a triangular wave oscillator for
timing generation, a high-gain error amplifier, and as totem pole output driver circuit which directly drives
the gate of power MOSFETs found in main switching devices. In addition, a pulse-by-pulse type, high-
speed, current-detection comparator circuit with variable detection level is incorporated which is required
for current mode control.
The HA17384SPS includes the above basic function circuits. In addition to these basic functions, the H
Series incorporates thermal shut-down protection (TSD) and overvoltage protection (OVP) functions, for
configuration of switching power supplies that meet the demand for high safety levels.
Between the HA17384 and HA17385, only the UVL threshold voltages differ as shown in the product
lineup table.(See next page.)
This IC is pin compatible with the “3842 family” ICs made by other companies in the electronics industry.
However, due to the characteristics of linear ICs, it is not possible to achieve ICs that offer full
compatibility in every detail.
Therefore, when using one of these ICs to replace another manufacturer’s IC, it must be recognized that it
has different electrical characteristics, and it is necessary to confirm that there is no problem with the power
supply (mounting) set used.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 2 of 30
Functions
Under-voltage lockout system
Reference voltage regulator of 5.0 V ± 2%
Triangular wave (sawtooth) oscillator
Error amplifier
Totem pole output driver circuit (direct driving for power MOS FETs)
Current-detection comparator circuit for current mode
OVP function (over voltage protection) *1
TSD function (thermal shut-down protection) *1
Protect function by zener diode (between power input and GND)
Note: 1. H series only.
Features
High-safety UVL circuit is used (Both VIN and Vref are monitored)
High speed operation:
Current detection response time: 100 ns Typ
Maximum oscillation frequency: 500 kHz
Low standby current: 170 µA Typ
Wide range dead band time
(Discharge current of timing capacitance is constant 8.4 mA Typ)
Able to drive power MOSFET directly
(Absolute maximum rating of output current is ±1 A peak)
OVP function (over voltage protection) is included *1
(Output stops when FB terminal voltage is 7.0 V Typ or higher)
TSD function (thermal shut-down protection) is included *1
(Output stops when the temperature is 160°C Typ or higher)
Zener protection is included
(Clamp voltage between VIN and GND is 34 V Typ)
Wide operating temperature range:
Operating temperature: 20°C to +105°C
Junction temperature: 150°C *2
Notes: 1. H series only.
2. S series only.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 3 of 30
Product Line-up
Package
Additional Function
UVL Power Supply
Threshold Voltage
DILP8 (DP-8)
SOP8 (FP-8DC)
TSD
(Thermal shut-
down protection)
OVP
(Over voltage
protection)
VTH UVL (V) Typ
VTL UVL (V) Typ
HA17384SPS HA17384SRP
HA17384HPS HA17384HRP
16.0 10.0
HA17385HPS HA17385HRP 8.4 7.6
Pin Arrangement
1
2
3
4
8
7
6
5
COMP
FB
CS
RT/CT
Vref
VIN
OUT
GND
(Top view)
Pin Function
Pin No. Symbol Function Note
1 COMP Error amplifier output pin
2 FB Inverting input of error amp./OVP input pin 1
3 CS Current sensing signal input pin
4 RT/CT Timing resistance, timing capacitance connect pin
5 GND Groung pin
6 OUT PWM Pulse output pin
7 VIN Power supply voltage input pin
8 Vref Reference voltage 5V output pin
Note: 1. Overvoltage protection (OVP) input is usable only for the HA17384H and HA17385H.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 4 of 30
Block Diagram
Oscillator
Totem pole
output circuit
Note: 1. Blocks with bold line are not included in HA17384SPS/SRP.
0.8mA
EA
+
OVP
+
CS
+
7.0V
UVL1
H
LVL VH
UVL2
Vref > 4.7V
R
Q
S
6.5V
1
2Vref
(2.5V)
*
1
2V
F
160°C
2R
R
1V
R
S
Q
PWM LOGIC
Vref
NOR
8.4 mA
1.2V
+
OR
34V
1
2
3
4
8
7
6
COMP
FB
(OVP input)
CS
RT/CT
Vref
V
IN
OUT
5 GND
2.8 V
OUT
5V band
gap
reference
regulator
OVP
latch
TSD
sense
CS
latch
Latch set
pulse
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 5 of 30
Absolute Maximum Ratings
Item Symbol Rating Unit Note
Supply voltage VIN 30 V
DC output current IO ±0.1 A
Peak output current IO PEAK ±1.0 A
Error amplifier input voltage VFB –0.3 to VIN V
COMP terminal input voltage VCOMP –0.3 to +7.5 V
Error output sink current IOEA 10 mA
Power dissipation PT 680 mW 1, 2
Operating temperature Topr –20 to +105 °C
125 °C 3 Junction temperature Tj
150 °C 4
–55 to +125 °C 3 Storage temperature Tstg
–55 to +150 °C 4
Notes: 1. For the HA17384HPS and HA17385HPS,
This value applies up to Ta = 43°C; at temperatures above this, 8.3 mW/°C derating should be
applied.
For the HA17384SPS,
This value applies up to Ta = 68°C; at temperatures above this, 8.3 mW/°C derating should be
applied.
Power Dissipation PT (mW)
Ambient Temperature Ta (°C)
680mW
374mW
43°C68°C150°C
800
600
400
200
0
20 0 20 40 60 80 100 120 140 160
166mW
105°C125°C
HA17384SPS
HA17384HPS, HA17385HPS
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 6 of 30
Absolute Maximum Ratings (cont.)
Notes: 2. This is the value when the device is mounted on a glass-epoxy substrate (40 mm × 40 mm × 1.6
mm). However,
For the HA17384HRP and HA17385HRP,
Derating should be performed with 8.3 mW/°C in the Ta 43°C range if the substrate wiring
density is 10%.
Derating should be performed with 11.1 mW/°C in the Ta 63°C range if the substrate wiring
density is 30%.
For the HA17384SRP,
Derating should be performed with 8.3 mW/°C in the Ta 68°C range if the substrate wiring
density is 10%.
Derating should be performed with 11.1 mW/°C in the Ta 89°C range if the substrate wiring
density is 10%.
Power Dissipation P
T
(mW)
Ambient Temperature Ta (°C)
374 mW
680 mW
43°C63°C150°C89°C
800
600
400
200
0
20 0 20 40 60 80 100 120 140 160
166 mW
500 mW
222 mW
68°C 105°C 125°C
HA17384SRP
: 11.1 mW/°C (wiring density is 30%)
: 8.3 mW/°C (wiring density is 10%)
HA17384HRP, HA17385HRP
: 11.1 mW/°C (wiring density is 30%)
: 8.3 mW/°C (wiring density is 10%)
3. Applies to the HA17384HPS/HRP and HA17385HPS/HRP.
4. Applies to the HA17384SPS/SRP.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 7 of 30
Electrical Characteristics
(The condition is: Ta = 25°C, VIN = 15 V, CT = 3300 pF, RT = 10 k without notice)
Reference Part
Item Symbol Min Typ Max Unit Test Condition Note
Reference output voltage Vref 4.9 5.0 5.1 V Io = 1 mA
Line regulation Regline 20 50 mV 12 V VIN 25 V
Load regulation Regload 10 25 mV 1 mA Io 20 mA
Output short current los 30 100 180 mA Vref = 0V
Temperature stability Vref 80 ppm/°C Io = 1 mA,
20°C Ta 105°C
1
Output noise voltage VN 100 µV 10 Hz fnoise 10 kHz 1
Note: 1. Reference value for design.
Triangular Wave Oscillator Part
Item Symbol Min Typ Max Unit Test Condition Note
Typical oscillating frequency fosc Typ 47 52 57 kHz CT = 3300 pF,
RT = 10 k
Maximum oscillating
frequency
fosc Max 500 kHz
Supply voltage dependency of
oscillating frequency
fosc 1 ±0.5 ±2.0 % 12 V VIN 25 V
Temperature dependency of
oscillating frequency
fosc 2 ±5.0 % 20°C Ta 105°C 1
Discharge current of CT IsinkCT 7.5 8.4 9.3 mA VCT = 2.0 V
Low level threshold voltage VTLCT 1.2 V 1
High level threshold voltage VTHCT 2.8 V 1
Triangular wave amplitude VCT 1.6 V VCT = VTHCT VTLCT 1
Note: 1. Reference value for design.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 8 of 30
Electrical Characteristics (cont.)
(The condition is: Ta = 25°C, VIN = 15 V, CT = 3300 pF, RT = 10 k without notice)
Error Amplifire Part / OVP Part
Item Symbol Min Typ Max Unit Test Condition Note
Non-inverting input voltage VFB 2.42 2.50 2.58 V VCOMP = 2.5 V
Input bias current IIB 0.2 2.0 µA VFB = 5.0 V
Open loop voltage gain AVOL 65 90 dB 2.0 V VO 4.0 V
Unity gain bank width BW 0.7 1.0 MHz
Power supply voltage
rejection ratio
PSRR 60 70 dB 12 V VIN 25 V
Output sink current IOsink EA 3.0 9.0 mA VFB = 2.7 V, VCOMP = 1.1 V
Output source current IOsource EA 0.5 0.8 mA VFB = 2.3 V, VCOMP = 5.0 V
High level output voltage VOH EA 5.5 6.5 7.5 V VFB = 2.3 V,
RL = 15 k(GND)
Low level output voltage VOL EA 0.7 1.1 V VFB = 2.7 V,
RL = 15 k(Vref)
OVP latch threshold
voltage
VOVP 6.0 7.0 8.0 V Increase FB terminal
voltage
1
OVP (FB) terminal input
current
IFB(OVP) 30 50 µA VFB = 8.0 V 1
OVP latch reset VIN voltage VIN(OVP RES) 6.0 7.0 8.0 V Decreasing VIN after OVP
latched
1
Note: 1. These values are not prescribe to the HA17384SPS/SRP because OVP function is not included.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 9 of 30
Electrical Characteristics (cont.)
(The condition is: Ta = 25°C, VIN = 15 V, CT = 3300 pF, RT = 10 k without notice)
Current Sensing Part
Item Symbol Min Typ Max Unit Test Condition Note
Voltage gain AVCS 2.85 3.00 3.15 V/V VFB = 0 V 1
Maximum sensing voltage VthCS 0.9 1.0 1.1 V
Power supply voltage
rejection ratio
PSRR 70 dB 12 V VIN 25 V 2
Input bias current IBCS 2 10 µA VCS = 2 V
Current sensing
response time
tpd 50 100 150 ns Time from when VCS
becomes 2 V to when
output becomes L (2 V)
3
Notes: 1. The gain this case is the ratio of error amplifier output change to the current-sensing threshold
voltage change.
2. Reference value for design.
3. Current sensing response time tpd is definded a shown in the figure 1.
V
CS
V
OUT
(PWM)
Vth
tpd
Figure 1 Definition of Current Sensing Response Time tpd
PWM Output Part
Item Symbol Min Typ Max Unit Test Condition Note
Output low voltage 1 VOL1 0.7 1.5 V losink = 20 mA
Output low voltage 2 VOL2 1.5 2.2 V losink = 200 mA 1
Output high voltage 1 VOH1 13.0 13.5 V losource = 20 mA
Output high voltage 2 VOH2 12.0 13.3 V losource = 200 mA 1
Output low voltage at
standby mode
VOL STB 0.8 1.1 V VIN = 5 V,
losink = 1 mA
Rise time tr 80 150 ns CL = 1000 pF
Fall time tf 70 130 ns CL = 1000 pF
Maximum ON duty Du max 94 96 100 %
Minimum ON duty Du min 0 %
Note: 1. Pulse application test
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 10 of 30
Electrical Characteristics (cont.)
(The condition is: Ta = 25°C, VIN = 15 V, CT = 3300 pF, RT = 10 k without notice)
UVL Part
Item Symbol Min Typ Max Unit Test Condition Note
14.5 16.0 17.5 V 1 Threshold voltage for
high VIN level
VTH UVL
7.6 8.4 9.2 V
Turn-ON voltage
when VIN is rising 2
9.0 10.0 11.0 V Minimum operating 1 Threshold voltage for
low VIN level
VTL UVL
6.8 7.6 8.4 V voltage after turn-ON 2
5.0 6.0 7.0 V 1 VIN UVL hysteresis voltage VHYS UVL
0.6 0.8 1.0 V
VHYS UVL = VTH UVL VTL UVL
2
Vref UVL threshold voltage VT Vref 4.3 4.7 Vref V Voltage is forced toVref
terminal
Notes: 1. For the HA17384S/H.
2. For the HA17385H.
Total Characteristics
Item Symbol Min Typ Max Unit Test Condition Note
Operating current IIN 7.0 10.0 13.0 mA CL = 1000 pF, VFB = VCS = 0 V
Standby current ISTBY 120 170 230 µA Current at start up
Current of latch ILATCH 200 270 340 µA VFB = 0 V after VFB = VOVP 1, 2
Power supply zener
voltage
VINZ 31 34 37 V IIN + 2.5 mA
Overheat protection
starting temperature
TjTSD 160 °C 3, 4
Notes: 1. These values are not prescribe to the HA17384SPS/SRP because OVP function is not included.
2. VIN = 8.5 V in case of the HA17384H.
2. These values are not prescribe to the HA17384SPS/SRP because TSD function is not included.
4. Reference value for design.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 11 of 30
Timing Chart
Waveform timing (Outline)Signal Name
Input voltage
VIN Pin 7
UVL1
Internal signal which
cannot be externally
monitored.
Reference voltage
Vref Pin 8
UVL2
Internal signal which
cannot be externally
monitored.
Oscillation voltage of
triangular wave
RT/CT Pin 4
Start up signal
Internal signal which
cannot be externally
monitored.
PWM latch setting signal
internal signal which
cannot be externally
monitored.
Error amplifier input signal
VFB Pin 2
Error amplifier output signal
VCOMP Pin 1
ID *1
OVP latch signal
Internal signal which
cannot be externally
monitored.
Power ON IC turn ON
Stationary operation
OVP input
OVP latched
condition
Power OFF
Reset of
OVP latch
Start up latch
release
( ) shows the case
using HA17385H
PWM output voltage
VOUT Pin 6
Note: 1. ID indicates the power MOSFET drain current; it is actually observed as voltage VS generated
by power MOSFET current detection source resistance RS.
VCOMP indicates the error amp output voltage waveform. Current mode operation is
performed so that a voltage 1/3 that of VCOMP is the current limiter level.
10 V
(7.6 V) 7.0 V
2 V
16 V
(8.4 V)
2 V
0V
0V
0V
0V
0V
0V
0V
0V
0V
0V
0V
5 V
4.7 V
2.8 V
1.2 V
7.0 V typ
(OVP input)
VCOMP
I
D
VIN
4.7 V
IC operates and
PWM output stops.
This voltage is determined
by the transformer
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 12 of 30
Operation (Description of Timing Chart)
From Power ON to Turn On
After the power is switched ON, the power supply terminal voltage (VIN) of this IC rises by charging
through bleeder resistor RB. At this time, when the power voltage is in the range of 2 V to 16 V*1. The
low-voltage, lock out UVL1 operates and accordingly the OUT voltage, that is, the gate voltage of the
power MOS FET, is fixed at 1.3 V or a lower value, resulting in the power MOS FET remaining in the OFF
state.
When the power supply voltage reaches 16 V, UVL1 of this IC is reset and the reference voltage (Vref)
generating part turns ON. However, until Vref becomes 4.7 V, the low-voltage, lock out UVL2 operates to
keep the OUT terminal voltage low. After Vref terminal voltage becomes 4.7 V or higher, OUT terminal
outputs a PWM pulse.
Note: 1. The value is for the HA17384S/H.
The value is 8.4 V for the HA17385H.
Generation of Triangular Wave and PWM Pulse
After the output of the Vref, each blocks begins to operate. The triangular wave is generated on the RT/CT
terminal. For PWM pulses, the triangular wave rise time is taken as the variable on-duty on-time. The
triangular wave fall time is taken as the dead-band time. The initial rise of the triangular wave starts from 0
V, and to prevent a large on-duty at this time, the initial PWM pulse is masked and not output. PWM
pulses are outputted after the second triangular wave. The above operation is enabled by the charge energy
which is charged through the bleeder resistor RB into the capacitor CB of VIN.
Stationary Operation
PWM pulses are outputted after the second wave of the triangular wave and stationary operation as the
switching power supply starts.
By switching operation from ON/OFF to OFF/ON in the switching device (power MOS FET), the
transformer converts the voltage. The power supply of IC VIN is fed by the back-up winding of the
transformer.
In the current mode of the IC, the current in the switcing device is always monitored by a source resistor
RCS. Then the current limiter level is varied according to the error voltage (COMP terminal voltage) for
PWM control. One third of the error voltage level, which is divided by resistors 2R and R in the IC, is
used to sense the current (R = 25 k).
Two diodes between the error output and the 2R-R circuit act only as a DC level shifter. Actually, these
diodes are connected between the 2R-R circuit and GND, and, the current sensing comparator and GND,
respectively. Therefore, these blocks operate 1.4 V higher than the GND level. Accordingly, the error of
the current sensing level caused by the switching noise on the GND voltage level is eliminated. The zener
diode of 1 V symbolically indicates that the maximum sensing voltage level of the CS terminal is 1 V.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 13 of 30
Power OFF
At power OFF, the input voltage of the transformer gradually decreases and then VIN of IC also decreases
according to the input voltage. When VIN becomes lower than 10 V*2 or Vref becomes lower than 4.7 V,
UVL1 (UVL2) operates again and the PWM pulse stops.
Note: 2. The value is for the HA17384S/H.
The value is 7.6 V for the HA17385H.
Commercial AC voltage
Power switch Line filter
Rectifier
bridge diode
DC
output
Floating
ground
Power MOSFET
ex. 2SK1567
SBD
ex. HRP24
OVP input
(Ex: from photocoupler)
20k
3.6k
100µ
200V
1000µ
10V
R
T
10k
V
CS
R
B
220k
1/4W
C
B
10µ
50V
V
IN
0.1µ
51
1k
+
B
PS
HRP32
Vref
V
IN
OUT
GND
COMP
FB
HA17384H,
HA17385H
CS
R
T
/C
T
+
+
+
+
R
CS
1
2W
100p
150k
330p
C
T
3300p
Figure 2 Mounting Circut Diagram for Operation Expression
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 14 of 30
V
COMP
COMP terminal
(Error output)
PWM pulse
Latch setting pulse
(Implemented in triagular
wave oscillator)
Latch setting
pulse
V
COMP
Error voltage
V
CS
Current sensing
level
R
S
Q
1 V
V
CS
CS terminal
2 R
R2V
F
×13
+CS
CS
latch
Figure 3 Operation Diagram of Current Sensing Part
Point:
Current Sense Comparator
Threshold Voltage VCS (V)
Error Amplifier Output Voltage Vcomp (V)
Light load
Heavy load
1) At maximum rated load, the setting should be made to give
approximately 90% of area A below.
2) When the OVP latch is operated, the setting should be made
in area B or C.
1.0
0.8
0.6
0.4
0.2
0.0012345678
B
A
C
1.4V 4.4V 7.5V
A : Stationary operation / PWM
(Current-mode operation)
B : Current limit operation / Max duty cycle
C : No sensitivity area / No PWM output
Figure 4 Current Sense Characteristics
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 15 of 30
Features and Theory of Current Mode Control
Features of Current Mode Control
Switch element current detection is performed every cycle, giving a high feedback response speed.
Operation with a constant transformer winding current gives a highly stable output voltage (with
excellent line regulation characteristics, in particular).
Suitable for flyback transformer use.
External synchronous operation is easily achieved. (This feature, for example, is applicable to
synchronization with a forizontal synchronizing signal of CRT monitor.)
Theory of Current Mode Control
In current mode control, a PWM pulse is generated not by comparing an error voltage with a triangular
wave voltage in the voltage mode, but by changing the current limiter level in accordance with the error
voltage (COMP terminal in this IC, that is,output of the error amplifier output) which is obtained by
constantly monitoring the current of the switching device (power MOS FET) using source resistor RCS.
One of the features of current mode control is that the current limited operates in all cycles of PWM as
described by the above theory.
In voltage mode, only one feedback loop is made by an output voltage. In current mode, on the other hand,
two loops are used. One is an output voltage loop and the other is a loop of the switching device current
itself. The current of the switching device can be controlled switch high speed. In current mode control,
the current in the transformer winding is kept constant, resulting in high stability. An important
consequence is that the line regulation in terms of total characteristics is better than that in voltage mode.
Transformar
AC
input
Current sense
comparator
Error amplifier
DC
output
RS
2R
R
R
S
IS
VCOMP Vref
OSC
+
+
Flip flop
Figure 5 Block Diagram of Current Mode Switching Power Spply
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 16 of 30
A. Control in the case of heavy load
B. Control in the case of light load
V
CS
I
S
V
CS
I
S
As the load becomes heavy and the DC output decreases, the current sensing
level is raised as shown in A. above in order to increase the current in the switching
device in each cycle. When the load decreases, inverse control is carried out as
shown in B. above.
Figure 6 Primary Current Control of Transformer in Current Mode (Conceptual Diagram)
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 17 of 30
Main Characteristics
Operating Current I
IN
(mA)
Operating Current I
IN
(mA)
Operating Current I
IN
(mA)
Power supply voltage V
IN
(V)
Ambient temperature Ta (°C)
Operating Current vs. Ambient Temperature
Standby Current/Latch Current vs. Supply Voltage
Exploded diagram of the small current part from the above figure
(HA17384S/H)
Power supply voltage V
IN
(V)
Standby Current/Latch Current vs. Supply Voltage
Exploded diagram of the small current part from the above figure
(HA17385H)
Power supply voltage V
IN
(V)
Power supply voltage V
IN
(V)
Ambient temperature Ta (°C)
20
15
10
5
0010203040
2.0
1.5
1.0
0.5
0
12
11
10
9
8
Ta = 25°C
Ta = 25°C
fosc = 52kHz
CT = 3300pF
RT = 10k
Ta = 25°C
fosc = 52kHz
CT = 3300pF
RT = 10k
20
15
10
5
0010203040
Ta = 25°C
010203040
2.0
1.5
1.0
0.5
0010203040
400
300
200
100
0
Supply Current vs. Supply Voltage (HA17384S/H) Supply Current vs. Supply Voltage (HA17385H)
Operating Current I
IN
(mA)
Operating Current I
IN
(mA)Standby Latch Current (µA)
Standby Current/Latch Current vs. Ambient Temperature
Latch current
(HA17384H)
Latch current
(HA17384H) Latch current
Stanby current
20 105806040200 20 105806040200
VIN = 15V
fosc = 52kHz
CT = 3300pF
RT = 10kLatch current
VIN = 15V (HA17384H)
VIN = 8.5V (HA17385H)
Latch current
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 18 of 30
Ambient temperature Ta (°C)
Ambient temperature Ta (°C)
Ambient temperature Ta (°C)
Supply voltage V
IN
(V)
Output current of Vref terminal (mA)
R
T
/C
T
terminal voltage V
CT
(V)
UVL Threshold Voltage vs. Ambient Temperature Line Regulation Characteristics of Reference Voltage
Load Regulation Characteristics of Reference Voltage Reference Voltage vs. Ambient Temperature
C
T
Discharge Current vs. R
T
/C
T
Terminal Voltage C
T
Discharge Current vs. Ambient Temperature
UVL voltage (V)
Reference voltage Vref (V)
Reference voltage Vref (V)
Reference voltage Vref (V)
C
T
discharge current I
CT
(mA)
20 5.2
5.1
5.0
4.9
4.8
6.0
5.5
5.0
4.5
4.0020 40 8060 100
Ta = 25°C
V
IN
= 15V
C
T
= 3300pF
R
T
= 10k
9.5
9.0
8.5
8.0
7.5
0123
15
10
5
0
5.2
5.1
5.0
4.9
4.8
Ta = 25°C
V
IN
= 15V
4
9.5
9.0
8.5
8.0
7.5
C
T
discharge current Isink
CT
(mA)
010 20 30
V
TL
V
TH
20 856040200
20 10560 8040200
20 10560 8040200
HA17385H
V
TH
HA17384S/H
V
TL
C
T
= 3300pF
R
T
= 10k
C
T
= 3300pF
R
T
= 10k
V
IN
= 15V
V
IN
=15 V
Ta = 25°C
V
IN
= 10V or more (HA17384S/H)
V
IN
= 7.6V or more (HA17385H)
Vref short
protection
operates
Measured when
R
T
/C
T
terminal voltage
is externally supplied
Minimum voltage of
triangular wave
Maximum voltage of
triangular wave
Measured when R
T
/C
T
terminal voltage of 2 V is
externally supplied
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 19 of 30
Oscillation frequency fosc (kHz)
Timing resistance R
T
()
500
200
100
50
20
10
5
500 1k 2k 5k 10k 20k 50k 100k 200k
Ta = 25°C
V
IN
= 15V
2200pF
4700pF
0.01µF
0.022µF
0.047µF
1000pF
CT= 470pF
Figure 7 Oscillation Frequency vs. Timing Resistance
Triangular wave
PWM maximum ON pulse
In the case of small C
T
and large R
T
(ex. C
T
= 3300pF, R
T
= 10k)
Du max = 95%
fosc = 52kHz
Triangular wave
PWM maximum ON pulse
In the case of large C
T
and small R
T
(ex. C
T
= 0.033µF, R
T
= 680)
Du max = 40%
fosc = 52kHz
Case 1.
Setting large maximum duty cycle.
Case 2.
Setting small maximum duty cycle.
Figure 8 Relationship Between Triangular Wave and Maximum ON Duty of PWM Pulse
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 20 of 30
Maximum ON duty Du max (%)
Timing Resistance R
T
()
Note: In the oscillation system of this IC, a constant discharging current of 8.4mA
flows the timing capacitor during triangular wave fall. Therefore, note that a
small maximum ON duty (large dead band) leads to a large supply current.
Refer to the equations of oscillation frequency and supply current for details.
100
75
50
25
0
500 1k 2k 5k 10k 20k 50k 100k 200k
Ta = 25°C
V
IN
= 15V
Figure 9 PWM Pulse ON Duty vs. Timing Resistance
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 21 of 30
Oscillation Frequency fosc (kHz)
Ambient Temperature Ta (°C)
Ambient temperature Ta (°C)
Ambient temperature Ta (°C)
Operating Current I
IN
(mA)
Maximum ON Duty Du max (%)
Output load capacitance C
L
(pF)
Oscillation Frequency vs. Ambient Temperature Operating Current vs. Maximum ON Duty
Rise/Fall Time of Output Pulse vs. Load Capacitance Rise/Fall Time of Output Pulse vs. Ambient Temperature
Rise/Fall Time (ns)
Rise/Fall Time (ns)
Current sensing level V
CS
(V)
V
IN
(UVL1)
Vref
(UVL2)
PWM
OUTPUT
Condition
description
L
L
L
L
H
L
H
H
L
Standby
state
IC is in
the ON
state and
output is
fixed to
LO.
Available
to
output
Current Sensing Level vs. Ambient Temperature Relationship Between Low Voltage Malfunction
Protection and PWM Output
Operation
state
Standby
state
H
L
65 25
025 50 75 100
V
IN
= 15V
fosc=50kHz
fosc=300kHz
V
CS
= 0V
V
FB
= 0V
250
0 1000 2000 3000
Fall Time tf
60
55
50
45
40
20
15
10
5
0
200
150
100
50
0
V
IN
= 15V
V
CS
= 0V
V
FB
= 0V
Ta = 25°C
C
T
= 3300pF
R
T
= 10k
4000
250
200
150
100
50
0
1.25
1.00
0.75
0.50
0.25
0
V
IN
= 15V
C
L
= 1000pF
C
T
= 3300pF
R
T
= 10k
Dumax = 95%
V
IN
= 15V
V
CS
= 0V
V
FB
= 0V
C
T
= 3300pF
R
T
= 10k
V
IN
= 15V
V
FB
= 0V
Rise time tr
C
L
= 1000pF
20 10560 8040200
20 10560 8040200
20 10560 8040200
C
T
= 0.033µF
R
T
= 680
Dumax = 40%
Ta=25°C
C
L
= 1000pF
Rise time t
r
Fall Time t
f
Measured when COMP terminal
voltage is externally supplied
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 22 of 30
Gain A
VO
(dB)
Error Amplifier Input Signal Frequency f (Hz)
Gain A
VO
100
75
50
25
0
25
Phase Φ (deg)
0
60
120
180
10 100 1k 10k 100k 1M 10M
Phase Φ
V
IN
= 15V, Ta = 25°C
Φ
O
= 60° Typ
Phase margin
at f
T
Unit gain frequency
f
T
= 1MHz Typ
Figure 10 Open Loop Gain Characterisrics of Error Amplifier
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 23 of 30
Triangular wave
PWM maximum
ON pulse
Dumax is the ratio of
maximum ON time of
PWM to one cycle time.
In the above case,
Dumax = 95%
Calculation of operation parameters
1. Maximum ON duty Du max (Refer to the right figure.)
Du max = 1
1 + 1.78 × In 1 + 190
RT 440
()
RT = + 440
190
0.56 (1/Du max 1)
CT = 1.78 ×Du max
fosc × RT
IDmax = VTHCS
fosc = 1
CT × RT × 0.56 + In 1 + 190
(){}
2. Oscillation frequency fosc
From the above two equations, the following two equations are
obtained.
3. Equalization to device RT from Du max
e
(e = 2.71828.base of natural logarithm)
4. Equation to device CT from fosc and RT
5. Operating current IIN
IIN = IQ + IsinkCT × (1 Du max) + Ciss × VIN × fosc
providing that IQ = 8.4mA Typ (Supply current when oscillation in IC stops.)
Ciss is the input gate capacitance of the power MOSFET which is connected and VIN is
the supply voltage of the IC.
Note that the actual value may differ from the calculated one because of the internal
delay in operation and input characteristics of the POWER MOS FET. Check the
value when mounting.
Additionally a small Dumax leads to a large supply current, even if the frequency is
not changed, and start up may become difficult. In such a case, the following
measure is recommended.
Example 1: Calculation when RT = 10k and CT = 3300pF
fosc = 52kHz, Du max = 95%, IIN = 9.7mA
Example 2: Calculation for 50% of Du max and 200 kHz of fosc
RT = 693, CT = 6360pF, IIN = 12.5mA
(1) For an AC/DC converter, a small bleeder resistance is required.
(2) The large capacitance between Vref and GND is required.
(3) Use a large Dumax with a triangular wave and raise the current limit of the
switching device to around the maximum value (1.0V Typ).
The current limit is expressed as
RT 440
However, Ciss = 1000pF, VIN = 18V
RCS
1
Figure 11 Calculation of Operation Parameters
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 24 of 30
Application Circuit Example (1)
Notes:
P
Snubber circuit
example
51
470p
1kV
FRD
DFG1C8
1. : PRIMARY GND, : SECONDARY GND.
2. Check the wiring direction of the transformer coil.
3. Insert a snubber circuit if necessary.
4. OVP function is not included in HA17384SPS/SRP.
Commercial
AC 100V
Rectifier bridge diode
Line filter
Transformer specification
example
EI-22 type core
(H7C18 × 06Z)
Gap length
lg = 0.3mm
Transformer coil example
P: 0.580T/570µH
S: 0.516T Bifiler/22µH
B: 0.244T/170µH
S
(Opetation Theory)
Because this circuit is a flyback type, the voltages in the
primary (P), secondary (s) coils of the transformer and
backup (B) coil are proportional to each other. Using this,
the output voltage of the backup coil (V
IN
of IC) is controlled
at constant 16.4V. (The voltage of the point divided by
resistors of 20k and 3.6kis 2.5V).
20k
3.6k
100µ
200V 1000µ
10V
R
T
10k
220k
1/4W
10µ
50V
V
IN
16.4V
0.1µ
51
1k
1k
+
B
PS
HRP32
DC 5V, 3A
OUTPUT
Vref
V
IN
OUT
GND
COMP
FB
HA17384H,
HA17385H
2SK1567
SBD
HRP24
CS
R
T
/C
T
+
+
+
+
1
2W
100p
150k
470p
C
T
3300p
141V
10k
2SA1029
HA17431
10k
47k
The circuit for
output current limiter
Figure 12 Primary Voltage Sensing Flyback Converter
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 25 of 30
Application Circuit Example (2)
Photocoupler
(for output control)
Commercial
AC 100V
Rectifier bridge diode
When the error amplifier is used
Line filter
Transformer specification
example
EI-22 type core
(H7C18 × 06Z)
Gap length
lg = 0.3mm
Transformer coil example
P: 0.580T/570µH
S: 0.516T Bifiler/22µH
B: 0.244T/170µH
(Operation Theory)
On the secondary side (S) of the flyback converter,
error amplification is carried out by a shunt
regulator and photocoupler.
The voltage of the backup coil (B) is not monitored,
which differs from the application example (1).
In addition, OVP operates on the secondary side
(S) using a photocoupler.
Refer to the application example (1) for the other
notes.
When the error
amplifier is not used
Bleeder resistor
(adjuster according
to the rating of the
Photocoupler)
100µ
200V
1000µ
10V
R
T
10k
220k
1/4W
10µ
50V
V
IN
16.4V
141V
0.1µ
51
1k
4.7k
+
B
PS
HRP32
DC
5V, 3A
OUTPUT
Vref
V
IN
OUT
GND
COMP
FB
HA17384H,
HA17385H
HA17431
2SK1567
SBD
HRP24
CS
R
T
/C
T
R
T
/C
T
+
+
+
+
1.8k
B
4.7k
1
2W
100p
150k
470p
C
T
3300p
330
3.3µ3.3k
+
Vref
V
IN
OUT
GND
FB
CS
0.8mA
COMP
OVP input
1k
47k HA17431
2SA1029 10k
10k
The circuit for
output current limiter
Figure 13 Secondary Voltage Sensing Flyback Converter
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 26 of 30
Application Examples for Fuller Exploitation of Power Supply Functions
A number of application examples are briefly described below.
1. Soft start
A soft start is a start method in which the PWM pulse width is gradually increased when the power
supply is activated. This prevents the stress on the transformer and switch element caused by a rapid
increase in the PWM pulse width, and also prevents overshoot when the secondary-side output voltage
rises. The circuit diagram is shown in figure 14.
+EA
I
O
800µA typ Vref
5V
(3V)
(4.4V) (3.7V)
(5V)
7V
IN
D
IN
V
REF
R
CU
C
ST
D2
D1
2
2.5V
IC internal circuit
(around error amp.) External circuit
(only partially shown)
FB
R1V
To power supply
detection
comparator
(1V)
COMP
8
1
2R
Figure 14 Circuit Diagram for Soft Start
Operation: In this circuit, error amp output source current IO (800 µA typ.) gradually raises the switch
element current detection level, using a voltage slope that charges soft start capacitance CST. When the
voltage at each node is at the value shown in parentheses in the figure, the soft start ends. The soft start
time is thus given by the following formula:
TST = (3.7 V/800 µA) × CST 4.62 CST (ms)
(CST unit: µF)
External parts other than CST operate as follows:
Diode D1 : Current detection level shift and current reverse-flow prevention.
Diode D2 : Together with diode DIN in the IC, CST charge drawing when power supply falls.
Resistance RCU : For CST charge-up at end of soft start. (Use a high resistance of the order of several
hundred k.)
Note: During a soft start, since PWM pulses are not output for a while after the IC starts operating, there
is a lack of energy during this time, and intermittent mode may be entered. In this case, the
capacitance between Vref and GND should be increased to around 4.7 µF to 10 µF.
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 27 of 30
Notice for Use
1. OVP Latch Block
Case
When DC power is applied directly as the power supply of the HA17384H, HA17385H, without using
the transformer backup coil. Also, when high-frequency noise is superimposed on the VIN pin.
Problem
The IC may not be turn on in the case of a circuit in which VIN rises quickly (10 V/100 µs or faster),
such as that shown in figure 15. Also, the OVP latch may operate even though the FB pin is normally
at VOVP or below after the IC is activated.
Reason
Because of the IC circuit configuration, the timer latch block operates first.
Remedy (counter measure)
Take remedial action such as configuring a time constant circuit (RB, CB) as shown in figure 16, to keep
the VIN rise speed below 10 V/100 µs. Also, if there is marked high-frequency noise on the VIN pin, a
noise cancellation capacitor (CN) with the best possible high-frequency characteristics (such as a
ceramic capacitor) should be inserted between the VIN pin and GND, and close to the VIN pin.
When configuring an IC power supply with an activation resistance and backup winding, such as an
AC/DC converter, the rise of VIN will normally be around 1 V/100 µs, and there is no risk of this problem
occurring, but careful attention must be paid to high-frequency noise.
Also, this phenomenon is not occuring to the HA17384S, because OVP function is not built-in.
OutputInput
V
IN
V
IN
GND
Feedback
HA17384
Series
Figure 15 Example of Circuit with Fast VIN Rise Time
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 28 of 30
OutputInput
Time constant
circuit
Feedback
HA17384
Series
VIN
VIN
18V
RB
51
CN
CB
1µF
GND
+
Figure 16 Sample Remedial Circuit
2. Externally Synchronized Operation
Case
When, with a power supply using the HA17384S/H or HA17385H, externally synchronized operation is
performed by applying an external syncronous signal to the RT/CT pin (pin 4).
Problem
Synchronized operation may not be possible if the amplitude of the external syncronous signal is too
large.
Reason
The RT/CT pin falls to a potential lower than the ground.
Remedy (counter measure)
In this case, clamping is necessary using a diode with as small a VF value as possible, such as a schottky
barrier diode, as shown in figure 17.
Vref
0.01µF
R
T
C
T
47
HA17384
Series
External
synchronous
signal
Figure 17 Sample Remedial Circuit
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 29 of 30
Package Dimensions
Hitachi Code
JEDEC
JEITA
Mass
(reference value)
DP-8B
Conforms
Conforms
0.51 g
14
58
9.6
10.6 Max
1.3
6.3
7.4 Max
2.54 Min
5.06 Max
2.54 ± 0.25 0.48 ± 0.10
7.62
0.25
+ 0.10
0.05
0.89
0˚ – 15˚
0.5 Min
1.27 Max
As of January, 2002
Unit: mm
Hitachi Code
JEDEC
JEITA
Mass
(reference value)
FP-8DC
Conforms
0.085 g
*Dimension including the plating thickness
Base material dimension
1.75 Max
4.90
0.25
0.15
0
˚
8
˚
M
85
14
1.27
3.95
0.40 ± 0.06
*0.42 ± 0.08
5.3 Max
0.75 Max
0.14
+ 0.11
0.04
0.20 ± 0.03
*0.22 ± 0.03
0.60
+ 0.67
0.20
6.10
+ 0.10
0.30
1.08
As of January, 2002
Unit: mm
HA17384SPS/SRP, HA17384HPS/HRP, HA17385HPS/HRP
Rev.2, Jul. 2002, page 30 of 30
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4. Design your application so that the product is used within the ranges guaranteed by Hitachi particularly
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conditions and other characteristics. Hitachi bears no responsibility for failure or damage when used
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7. Contact Hitachis sales office for any questions regarding this document or Hitachi semiconductor
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