UNISONIC TECHNOLOGIES CO., LTD
TDA2030A LINEAR INTEGRATED CIRCUIT
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Copyright © 2007 Unisonic Technologies Co., Ltd QW-R107-005,C
18W HI-FI AUDIO AMPLIFIER
AND 35W DRIVER
DESCRIPTION
The UTC TDA2030A is a monolithic IC intended for use as
low frequency class AB amplif ier.
With Vs=max=44V it is particularly suited for more reliable
applications without regulated supply and for 35W driver circuits
using low-cost complementary pairs.
The UTC TDA2030A provides high output current and has
very low harmonic and cross-over distortion.
Further the device incorporates a short circuit protection
system comprising and arrangem ent for automatically limiting
the dissipated power so as to keep the working point of the
output transistors within their safe operating area. A
conventional thermal shut-down system is also inclu de d.
*Pb-free plating product number: TDA2030AL
ORDERING INFORMATION
Ordering Number
Normal Lead Free Plating Package Packing
TDA2030A-TA5-T TDA2030AL-TA5-T TO-220-5 Tube
TDA2030A-TB5-T TDA2030AL-TB5-T TO-220B Tube
TDA2030AL-TA5-T (1)Packing Type
(2)Package Type
(3)Lead Plating
(1) T: Tube
(2) TA5: TO-220-5, TB5: TO-220B
(3) L: Lead Free Plating, Blank: Pb/Sn
PIN CONFIGURATION
PIN NO. PIN NAME
1 Non inverting input
2 Inverting input
3 -VS
4 Output
5 +VS
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ABSOLUTE MAXIMUM RATINGS (Ta=25°C)
PARAMETER SYMBOL RATINGS UNIT
Supply Voltage Vs ±22 V
Input Voltage VIN Vs V
Differential Input Voltage VI(DIFF) ±15 V
Peak Output Current(internally lim ited) IOUT 3.5 A
Total Power Dissipation at Tc=90°C PD 20 W
Junction Temperature TJ -40 ~ +150 °C
Storage Temperature TSTG -40 ~ +150 °C
Note: Absolute maximum ratings are thos e values beyond which the device could be permanently damaged.
Absolute maximum ratings are stress ratings only and functional devic e operation is not implied.
ELECTRICAL CHARACTERISTICS (Refer to the test circuit, Vs =±16V, Ta=25°C)
PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT
Supply Voltage Vs ±6 ±22 V
Quiescent Drain Current IQ 50 80 mA
Input Bias Current II(BIAS) 0.2 2 µA
Input Offset Voltage VI(OFF) ±2 ±20 mV
Input Offset Current II(OFF) Vs=±22V ±20 ±200 nA
Power Bandwidth BW P
OUT =15W,RL=4Ω 100 KHz
RL=4Ω 15 18 W
RL=8Ω 10 12
W
Output Power POUT d=0.5%,Gv=26dB,
f=40Hz to 15KHz Vs=±19V,
RL=8Ω 13 16 W
Open Loop Voltage Gain Gvo 80 dB
Closed Loop Voltage Gain Gvc f=1kHz 25.5 26 26.5 dB
POUT =0.1 to 14W, RL=4Ω
f=40Hz to 15KHz 0.08 %
POUT =0.1 to 14W, RL=4Ω
f=1kHz 0.03 %
Distortion d
POUT =0.1 to 9W, RL=8Ω
f=40Hz to 15KHz 0.5 %
Second Order CCIF Intermodulation
distortion d2 POUT =4W, RL=4Ω
f2-f1=1KHz 0.03 %
Third Order CCIF Intermodulation
Distortion d3 f1=14KHz, f2=15KHz 0.08 %
Slew rate SR 8 V/µ sec
POUT =15W 106 dB
Signal to Noise Ratio S/N RL=4Ω, Rg=10kΩ,
B=curve A POUT =1W 94 dB
Input Noise Voltage eN B=curve A
B= 22Hz to 22KHz 2
3
10 µV
Input Noise Current iN B=curve A
B= 22Hz to 22KHz 50
80
200 pA
Input Resistance (pin 1) RIN Open loop, f=1KHz 0.5 5 MΩ
Supply Voltage Rejection SVR RL=4Ω, Gv=26dB
Rg=22KΩ, f=100Hz 54 dB
Thermal Shut-Down Junction
Temperature TJ 145 °C
TDA2030A LINEAR INTEGRATED CIRCUIT
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APPLICATION CIRCUIT
TDA2030A LINEAR INTEGRATED CIRCUIT
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TEST CIRCUIT
UTC
TDA2030A
1
23
5
4
VIN
+Vs
-Vs
C1
1 F
C2
22 FC6
100 FC4
100nF C7
220nF
C3
100nF
C5
220 FD1
1N4001
D1
1N4001
R3
22k
R1
13k
R4
1
RL
R3
680
SINGLE SUPPLY AMPLIFIER
UTC
TDA2030A
1
23
5
4
VIN
+Vs
0.1 F
100k
RL=4
4.7k
1N4001
2.2 F
100k
2.2 F
100k
22 F
220 F
2200 F
1N4001
R4
1
C7
220nF
C
R
100k
TDA2030A LINEAR INTEGRATED CIRCUIT
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TYPICAL CHARACTERISTICS
102103104105106107
101
-60
-20
20
60
100
140
Phase
Gain
Gv(dB)
180
90
0
Phase
Open Loop Frequency Response
24 28 32 36 40 44
24
4
8
12
16
20
RL=4
RL=8
Gv=26dB
d=0.5%
f=40 to 15kHz
Output Power vs. Supply Voltage
Total Harmonic Distortion vs.
Output Power Two Tone CCIF Intermodulation
Distortion
10
-1 100101102
10
-2
10
-2
10
-1
100
101
102
Vs=38V
RL=8
Vs=32V
RL=4
f=15kHz
f=1kHz
Gv=26dB
101102
10
-2
10
-1
100
101
102
103104105
Order (2f1-f2)
Order (2f2-f1)
Vs=32V
PoUT=4W
RL=4
Gv=26dB
Large Signal Frequency Response Maximum Allowable Power
Dissipation vs. Ambient Temperture
101102103104
30
5
10
15
20
25
Vs=±15V
RL=4
Vs=±15V
RL=8
-50 0 50 100 150 200
30
5
10
15
20
25
infinite heatsink
heatsink having
Rty=25°C/W
heatsink having
Rth=4°C/W
heatsink having
Rth=8°C/W
Ambient Temperture, Ta (℃)
Maximum Allowable Power
Dissipation, PD(W)
Frequency (kHz)
Vo(Vp-p)
Output Power, PoUT (W) Frequency (Hz)
Supply Voltage, Vs (V)
Frequency (Hz)
Output Power, PoUT (W)
Total Harmonic Distortion, d( % )
Total Harmonic Distortion, d( % )
PoUT (W)
TDA2030A LINEAR INTEGRATED CIRCUIT
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UTC
TDA2030A
1
23
54
VIN
+Vs
C3
0.22 F
R3
56k
RL=4
R4
3.3k
1N4001
C4
10 F
R1
56k
C1
0.22 F
R2
56k
C2
47 F
C5
2200 F
/40V
C8
2200 F
R6
1.5
C6
0.22 F
R5
30k
R7
1.5
1N4001
R8
1
C7
0.22 F
Fig. 1 Single supply hig h power amplifier
TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 1
PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT
Supply Voltage Vs 36 44 V
Quiescent Drain Current IQ Vs=36V 50 mA
d=0.5%, RL=4Ω
f=40Hz to 15kHz, Vs=39V 35
d=0.5%, RL=4Ω
f=40Hz to 15kHz, Vs=36V 28
d=10%, f=1kHz,
RL=4Ω, Vs=39V 44
Output Power POUT
d=10%,RL=4Ω
f=1kHz,Vs=36V 35
W
Voltage Gain Gv f=1kHz 19.5 20 20.5 dB
Slew Rate SR 8 V/µsec
POUT=20W, f=1kHz 0.02 %
Total Harmonic Distortion d POUT=20W, f=40Hz to 15kHz 0.05 %
Input Sensitivity VIN Gv=20dB, POUT=20W,
f=1kHz, RL=4Ω 890 mV
RL=4Ω, Rg=10kΩ
B=curve A, POUT=25W
108
Signal to Noise Ratio S/N RL=4Ω, Rg=10kΩ
B=curve A, POUT=4W 100
dB
TDA2030A LINEAR INTEGRATED CIRCUIT
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TYPICAL CHARACTERISTICS(Cont.)
24 28 32 34 36 40
5
15
25
35
45
Output Power vs. Supply Voltage
Output Power, PoUT (W)
Supply Voltage, Vs (V) 10-1 100101
10-2
10-1
100
f=15kHz
f=1kHz
Vs=36V
RL=4
Gv=20dB
Total Harmonic Distortion, d (%)
Output Power, PoUT (W)
Total Harmonic Distortion vs. Output Power
100 250 400 550 700
0
5
10
15
20 Gv=26dB
Gv=20dB
Input Level, Vi (mV)
Output Power, POUT (W)
Output Power vs. Input Level
0
5
10
15
20
0 8 16 24 32
Power Dssipation, PD(W)
Complete
Amplifier
UTC
TDA2030
Power Dssipation vs. Output Power
Output Power, PoUT (W)
TDA2030A LINEAR INTEGRATED CIRCUIT
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TYPICAL AMPLIFIER WITH SPLIT POWER SUPPLY
BRIDGE AMPLIFIER WITH SPLIT POWER SUPPLY (POUT=34W, VS=16V, VS=-16V)
TDA2030A LINEAR INTEGRATED CIRCUIT
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MULTIWAY SPEAKER SYSTEMS AND AC TIVE BOXES
Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is
specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems
divide the audio spectrum two or three bands.
To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must
overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to
ensure that each unit generates the correct amount of aco ustic ener gy for its s egments of the audio sp ectrum. In this
respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies
of the crossover filters (see Fig. 2). As an exam ple, a 100W three-way system with crossover frequ encies of 400Hz
and 3KHz would require 50W for the woofer, 35W for the midrange un it and 15W for the tweeter.
Both active and passive filters can be used for crossovers but active filters cost significantly less than a good
passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the
typical defects of passive filters:
--Power less;
--Increased impedance seen by the loudspeaker (lower damping)
--Difficulty of precise design due to variable loudspeaker impedance.
Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it
particularly interesting and economically sou nd to use monolithic power amplifiers.
In some applications complex filters are not relay necessary and simple RC low-pass and high-pass networks
(6dB/octave) can be recommend ed.
T he result obtained are excellent because this is the best type of audio filter and the only one free from phase and
transient distortion.
The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well
beyond the crossover frequency to avoid distortion.
A more effective solution is shown in Fig. 3.
The proposed circuit can realize combined power amplifi ers and 1 2dB/octave high-pass or low-pass filters.
In proactive, at the input pins amplifier t wo equal and in-phase voltages are available, as required for the active
filter operations.
The impedance at the Pin (-) is of the order of 100Ω, while that of the Pin (+) is very high, which is also what was
wanted.
The components values calcul ated for fc=900Hz using a Bessel 3rd Sallen and Key structure are:
C1=C2=C3=22nF, R1=8.2KΩ, R2=5.6KΩ, R3=33KΩ.
Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown as below.
It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz.
The midrange section consist ors of two filter s a high pass circuit foll owed by a lo w pass net work. With Vs=36V the
output power delivered to the woofer is 25W at d=0.06% (30W at d= 0.5%).The power delivered to the m idrange and
TDA2030A LINEAR INTEGRATED CIRCUIT
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the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance
(RL=4Ω to 8Ω).
It is quite common that midrange and tweeter speakers have an efficie ncy 3dB higher than woofers.
3WAY 60W ACTIVE LOUDSPEAKER SYSTEM (Vs=36V)
1
2
54
3
UTC
TDA2030A
1
2
54
3
UTC
TDA2030A
1
2
54
3
UTC
TDA2030A
0.22 F2200 F
18nF
33nF
100 F
0.22 F
1N4001
1 F
0.1 F0.1 F
0.22 FVs+
18nF
3.3nF
100 F
0.22 F
3.3nF3.3nF
47 F
0.22 F
100 F
0.22 F
220 F
0.22 F
2200 F
1N4001
BD908
BD907
22k
1
4
1.5
1.5
3.3k
22k
22k
680
100
1
22k22k
6.8k
3.3k
100
2.2k
Vs+
1N4001
1N4001
1N4001
8
1
2.2k
12k
100
22k
8
22k
22k
Vs+
100 F
Vs+
IN
Woofer
Midrange
Tweeter
High-pass
3KHz
High-pass
3KHz
Band-pass
300Hz to 3kHz
Low-pass
300Hz
1N4001
MUSICAL INSTRUMENTS AMPLIFIERS
Another important field of appl ication for active system is music.
In this area the use of several medium power amplifiers is more convenie nt than a single h igh po wer amplifier, and
it is also more reliable. A typical example (see Fig. 4) consist of four amplifiers each driving a low-cost, 12 inch
loudspeaker. This applic ation can supply 80 to 160W rms.
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TRANSIENT INTER-MODULATION DISTORTION(TIM)
Transient inter-modulatio n distortion is an unfortunate phenomena associated with negative-feedback amplifiers.
When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency
components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation
distortion will be produced as in Fig.5. Since transients occur frequently in music this obviously a problem for the
designed of audio amplifi ers. Unfortunately, heav y negative feedback is frequenc y used to reduc e the total harmonic
distortion of an amplifier, which tends to aggravate the transient inter-modulation (TIM situation.)
20 to 40W
Amplifier
20 to 40W
Amplifier
20 to 40W
Amplifier
20 to 40W
Amplifier
PRE AMPLIFIER POWER
AMPLIFIER
FEEDBACK
PATH
INPUT
V1 V2 V3 V4
¦ÂV4
OUTPUT
V1
V2
V3
V4
Fig.4 High Power Active Box For Musical Instrument Fig.5 Overshoot Phenomenon In Feedback Amplifiers
The best known method for the measurement of TIM consists of feeding sine waves superimposed onto square
wavers, into the amplifier under test. The output spectrum is then examined using a spectrum analyzer and
compared to the input. This method suffers from serious disadvantages: the accurac y is limited, the measurement is
a tatter delicate operation and an expensive spectrum analyzer is essential.
The "inverting-sawtooth" method of measurement is based on th e response of an amplifier to a 20KHz saw-tooth
wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. T he output will
follow the upper line in Fig. 6 cutting of the shade area and thus increasing the mean level. If this output signal is
filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is
difficult to measure because it is indist inguishable from the DC offset of the amplifier. This problem is neatly avoide d
in the IS-TIM method by periodically i nverti ng the sa w-toot h wave-form at a low audio frequency as s hown in Fig.7.In
the case of the saw-tooth in Fig. 8 the mean level was increased by the TIM distortion, for a saw-tooth in the other
direction the opposite is true.
m2
m1
SR(V/ s) Input
Signal
Filtered
Output
Siganal
Fig.6 20kHz Sawtooth Waveform Fig. 7 Inverting Sawtooth Waveform
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The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured
easily with an oscilloscop e. If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are
measured, the TIM can be found very simply from:
100*
Vsawtooth
VOUT
TIM =
TIM(%)
TIM=0.1%
TIM=0.01%
TIM=1%
SR(V/μs)
In Fig.8 The experimental results are shown for the 30W amplifier using the UTC TDA2030A as a driver and a
low-cost complementary pair. A simple RC fi lter on th e input of the amplifi er to limit the m aximum signal slope(SS) is
an effective way to reduce TIM.
The Diagram of Fig.9 can be used to find the Slew-Rate(SR) required for a given output power or voltage and a
TIM design target.
For example if an anti-TIM filter with a cutoff at 30kHz is us ed and the ma x. peak to pea k output voltage is 2 0V then,
referring to the diagram, a Slew-Rate of 6V/µs is necessary for 0.1% TIM.
As shown Slew-Rates of above 10V/µs do not contribute to a further reduction in TIM.
Slew-Rates of 100V/µs are not only useless but also a disadvantage in hi-fi audio amplif iers because they tend to
turn the amplifier into a radio receiver.
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POWER SUPPLY
Using monolithic audio amplifier with non regulat ed suppl y correctly. In any working case it must provide a suppl y
voltage less than the maximu m value fixed by the IC breakdo wn voltage.
It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage
variations with and without load. The UTC TDA2030A(Vsmax=44V) is particularly suitable for substitution of the
standard IC power amplifiers(with Vsmax=36V) for more reliable applications.
An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the
diagram of Fig. 10.
A regulated supply is not usually used for the power output stages because of its dimensioning must be done
taking into account the power to supply in signal peaks. They are not only a small percentage of the total music
signal, with consequently large overdimensioning of the circuit.
Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the
additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer
designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the
required energy.
In average conditions, the continuous po wer supplied is lower. The music power/continuous po wer ratio is greater
in case than for the case of regulated supplied, with space saving and cost reduction.
0 0.4 0.8 1.2 1.6 2.0
28
30
32
34
36
VoUT(V)
IoUT(A)
Fig. 10 DC characteristics of 50W non-regulated supply
3300 F
220V
0
2
4
Ripple (Vp-p)
Ripple
Vout
VoUT
DC Output Voltage(Vo) Mains(220V) Secondary Voltage Io=0 Io=0.1A Io=1A
+20% 28.8V 43.2V 42V 37.5V
+15% 27.6V 41.4V 40.3V 35.8V
+10% 26.4V 39.6V 38.5V 34.2V
24V 36.2V 35V 31V
-10% 21.6V 32.4V 31.5V 27.8V
-15% 20.4V 30.6V 29.8V 26V
-20% 19.2V 28.8V 28V 24.3V
TDA2030A LINEAR INTEGRATED CIRCUIT
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SHORT CIRCUIT PROTECTION
The UTC TDA2030A has an original circuit which limits the current of the output transistors. This function can be
considered as being peak p ower limiting rather than simple current lim iting. It reduces the possibility that the dev ice
gets damaged during an accid ental short circuit from AC output to Ground.
THERMAL SHUT- DOW N
The presence of a thermal limiting circuit offers the following advantages :
1).An overload on the output (even if it is permanent), or an above limit ambient temperature can be easily
supported since the T J can not be higher than 150°C
2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no
possibility of device damage due to high junction temperature increase up to 150°C, the thermal shut-down
simply reduces the power dissipation and the current consumption.
APPLICATION SUGGESTION
The recommended values of the components are those shown on application circuit of TYPICAL AMPLIFIER
WITH SPLIT POWER SUPPLY. Different values can be used. The following table can help the desi gn er.
COMPONENT RECOMMENDED VALUE PURPOSE LARGER THAN
RECOMMENDED
VALUE
SMALLER THAN
RECOMMENDED
VALUE
R1 22KΩ Closed loop gaon
setting. Increase of Gain Decrease of Gain
R2 680Ω Closed loop gaon
setting. Decreas e of Gain Increase of Gain
R3 22KΩ Non inverting input
biasing Increase of input
impedance Decrease of input
impedance
R4 1Ω Frequency stability
Danger of oscillation
at high frequencies
with inductive loads.
R5 ≈3R2 Upper frequency
cutoff Poor high frequencies
attenuation Danger of oscillation
C1 1µF Input DC decoupling Increase of low
frequencies cutoff
C2 22µF Inverting DC
decoupling Increase of low
frequencies cutoff
C3,C4 0.1µF Supply voltage bypass Danger of oscillation
C5,C6 100µF Supply voltage bypass Danger of oscillation
C7 0.22µF Frequency stability Larger bandwidth
C8 ≈1/(2π*B*R1) Upper frequency
cutoff smaller bandwidth Larger bandwidth
D1,D2 1N4001
To protect the device
against output voltage
spikes.
UTC assumes no responsibility for equipment failures that result from using products at values that
exceed, even momentarily, rated values (such as maximum ratings, operating condition ranges, or
other param eters) l isted in products specif icati ons of any and all UTC products described or contai ned
herein. UTC products are not designed for use in life support appliances, devices or systems where
m al funct ion of these pr oduct s can be reasonably ex pected to result i n personal injur y. Reproducti on in
whole or in part is prohibited without the prior written consent of the copyright owner. The inf ormation
presented in this docum ent does not f orm part of any quotat ion or cont ract, i s beli ev ed to be accurat e
and rel iable and may be c hanged wit hout notic e.
