LMV651MFX/NOPB - NATIONAL SEMICONDUCTOR

LMV651,LMV652,LMV654

LMV651/LMV652/LMV654 12 MHz, Low Voltage, Low Power Amplifiers

Literature Number: SNOSAI7I

October 8, 2008

LMV651/LMV652/LMV654

12 MHz, Low Voltage, Low Power Amplifiers

General Description

National’s LMV651/LMV652/LMV654 are high performance,

low power operational amplifier ICs implemented with

National's advanced VIP50 process. This family of parts fea-

tures 12 MHz of bandwidth while consuming only 116 μA of

current, which is an exceptional bandwidth to power ratio in

this op amp class. The LMV651/LMV652/LMV654 are unity

gain stable and provide an excellent solution for general pur-

pose amplification in low voltage, low power applications.

This family of low voltage, low power amplifiers provides su-

perior performance and economy in terms of power and

space usage. These op amps have a maximum input offset

voltage of 1.5 mV, a rail-to-rail output stage and an input com-

mon-mode voltage range that includes ground. The LMV651/

LMV652/LMV654 provide a PSRR of 95 dB, a CMRR of 100

dB and a total harmonic distortion (THD) of 0.003% at 1 kHz

frequency and 2 kΩ load.

The operating supply voltage range for this family of parts is

from 2.7V and 5.5V. These op amps can operate over a wide

temperature range (−40°C to 125°C) making them ideal for

automotive applications, sensor applications and portable

equipment applications. The LMV651 is offered in the ultra

tiny 5-Pin SC70 and 5-Pin SOT-23 package. The LMV652 is

offered in an 8-Pin MSOP package. The LMV654 is offered

in a 14-Pin TSSOP package.

Features

(Typical 5V supply, unless otherwise noted.)

■Guaranteed 3.0V and 5.0V performance

■Low power supply current

—LMV651 116 μA

—LMV652 118 μA per amplifier

—LMV654 122 μA per amplifier

■High unity gain bandwidth 12 MHz

■Max input offset voltage 1.5 mV

■CMRR 100 dB

■PSRR 95 dB

■Input referred voltage noise 17 nV/√Hz

■Output swing with 2 kΩ load 120 mV from rail

■Total harmonic distortion 0.003% @ 1 kHz, 2 kΩ

■Temperature range −40°C to 125°C

Applications

■Portable equipment

■Automotive

■Battery powered systems

■Sensors and Instrumentation

20123861

High Gain Wide Bandwidth Inverting Amplifier

20123806

Open Loop Gain and Phase vs. Frequency

LMV651/LMV652/LMV654 12 MHz, Low Voltage, Low Power Amplifiers

Absolute Maximum Ratings (Note 1)

If Military/Aerospace specified devices are required,

please contact the National Semiconductor Sales Office/

Distributors for availability and specifications.

ESD Tolerance (Note 2)

Human Body Model 2000V

Machine Model 100V

Differential Input VID ±0.3V

Supply Voltage (VS = V+ - V−)6V

Input/Output Pin Voltage V+ +0.3V, V− −0.3V

Storage Temperature Range −65°C to 150°C

Junction Temperature (Note 3) 150°C

Soldering Information

Infrared or Convection (20 sec) 235°C

Wave Soldering Lead Temp (10

sec) 260°C

Operating Ratings (Note 1)

Temperature Range (Note 3) −40°C to 125°C

Supply Voltage 2.7V to 5.5V

Package Thermal Resistance (θJA)(Note 3)

5-Pin SC70 456°C/W

5-Pin SOT-23 234°C/W

8-Pin MSOP 234°C/W

14-Pin TSSOP 160°C/W

3V DC Electrical Characteristics

Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 3V, V− = 0V, VO = VCM = V+/2, and RL > 1 MΩ. Bold-

face limits apply at the temperature extremes.

Symbol Parameter Conditions Min

(Note 5)

Typ

(Note 4)

Max

(Note 5)

Units

VOS Input Offset Voltage 0.1 ±1.5

2.7

TC VOS Input Offset Average Drift 6.6 μV/°C

IBInput Bias Current (Note 6) 80 120 nA

IOS Input Offset Current 2.2 15 nA

CMRR Common Mode Rejection Ratio 0 ≤ VCM≤ 2.0 V 87

100 dB

PSRR Power Supply Rejection Ratio 3.0 ≤ V+ ≤ 5V, VCM = 0.5 87

95 dB

2.7 ≤ V+ ≤ 5.5V, VCM = 0.5 87

CMVR Input Common-Mode Voltage

Range

CMRR ≥ 75 dB

CMRR ≥ 60 dB

2.1

AVOL Large Signal Voltage Gain 0.3 ≤ VO ≤ 2.7, RL = 2 kΩ to V+/2

0.4 ≤ VO ≤ 2.6, RL = 2 kΩ to V+/2

0.3 ≤ VO ≤ 2.7, RL = 10 kΩ to V+/2

0.4 ≤ VO ≤ 2.6, RL = 10 kΩ to V+/2

VOOutput Swing High RL = 2 kΩ to V+/2 80 95

120

mV from

rail

RL = 10 kΩ to V+/2 45 50

Output Swing Low RL = 2 kΩ to V+/2 95 110

125

RL = 10 kΩ to V+/2 60 65

ISC Maximum Continuous Output

Current

Sourcing (Note 8) 17 mA

Sinking (Note 8) 25

ISSupply Current per Amplifier LMV651 115 140

175 μA

LMV652 118

LMV654 122

SR Slew Rate AV = +1,

10% to 90% (Note 7)

3.0 V/μs

GBW Gain Bandwidth Product 12 MHz

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LMV651/LMV652/LMV654

Symbol Parameter Conditions Min

(Note 5)

Typ

(Note 4)

Max

(Note 5)

Units

enInput-Referred Voltage Noise f = 100 kHz 17 nV/

f = 1 kHz 17

inInput-Referred Current Noise f = 100 kHz 0.1 pA/

f = 1 kHz 0.15

THD Total Harmonic Distortion f = 1 kHz, AV = 2, RL = 2 kΩ 0.003 %

5V DC Electrical Characteristics

Unless otherwise specified, all limits are guaranteed for TJ = 25°C, V+ = 5V, V− = 0V,VO = VCM = V+/2, and RL > 1 MΩ. Boldface

limits apply at the temperature extremes.

Symbol Parameter Conditions Min

(Note 5)

Typ

(Note 4)

Max

(Note 5)

Units

VOS Input Offset Voltage 0.1 ±1.5

2.7

TC VOS Input Offset Average Drift 6.6 μV/°C

IBInput Bias Current (Note 6) 80 120 nA

IOS Input Offset Current 2.2 15 nA

CMRR Common Mode Rejection Ratio 0 ≤ VCM≤ 4.0 V 90

100 dB

PSRR Power Supply Rejection Ratio 3V ≤ V+ ≤ 5V, VCM = 0.5V 87

95 dB

2.7V ≤ V+ ≤ 5.5V, VCM = 0.5V 87

CMVR Input Common-Mode Voltage

Range

CMRR ≥ 80 dB

CMRR ≥ 68 dB

4.1

AVOL Large Signal Voltage Gain 0.3 ≤ VO ≤ 4.7V, RL = 2 kΩ to V+/2

0.4 ≤ VO ≤ 4.6, RL = 2 kΩ to V+/2

0.3 ≤ VO ≤ 4.7V, RL = 10 kΩ to V+/2

0.4 ≤ VO ≤ 4.6, RL = 10 kΩ to V+/2

VOOutput Swing High RL = 2 kΩ to V+/2 120 140

185

mV from

rail

RL = 10 kΩ to V+/2 75 90

120

Output Swing Low RL = 2 kΩ to V+/2 110 130

150

RL = 10 kΩ to V+/2 70 80

ISC Maximum Continuous Output

Current

Sourcing (Note 8) 18.5 mA

Sinking (Note 8) 25

ISSupply Current per Amplifier LMV651 116 140

175 μA

LMV652 118

LMV654 122

SR Slew Rate AV = +1, VO = 1 VPP

10% to 90% (Note 7)

3.0 V/μs

GBW Gain Bandwidth Product 12 MHz

enInput-Referred Voltage Noise f = 100 kHz 17 nV/

f = 1 kHz 17

inInput-Referred Current Noise f = 100 kHz 0.1 pA/

f = 1 kHz 0.15

THD Total Harmonic Distortion f = 1 kHz, AV = 2, RL = 2 kΩ 0.003 %

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LMV651/LMV652/LMV654

Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is

intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics

Tables.

Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC)

Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC).

Note 3: The maximum power dissipation is a function of TJ(MAX, θJA, and TA. The maximum allowable power dissipation at any ambient temperature is

PD = (TJ(MAX) - TA)/ θJA. All numbers apply for packages soldered directly onto a PC board.

Note 4: Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary over time and will

also depend on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material.

Note 5: Limits are 100% production tested at 25°C. Limits over the operating temperature range are guaranteed through correlations using Statistical Quality

Control (SQC) method.

Note 6: Positive current corresponds to current flowing into the device.

Note 7: Slew rate is the average of the rising and falling slew rates.

Note 8: The part is not short circuit protected and is not recommended for operation with low resistive loads. Typical sourcing and sinking output current curves

are provided in the Typical Performance Characteristics and should be consulted before designing for heavy loads.

Connection Diagrams

5-Pin SC70/ SOT-23

20123802

Top View

8-Pin MSOP

20123803

Top View

14-Pin TSSOP

20123804

Top View

Ordering Information

Package Part Number Package Marking Transport Media NSC Drawing

5-Pin SC70 LMV651MG A93 1k Units Tape and Reel MAA05A

LMV651MGX 3k Units Tape and Reel

5-Pin SOT-23 LMV651MF AY2A 1k Units Tape and Reel MF05A

LMV651MFX 3k Units Tape and Reel

8-Pin MSOP LMV652MM AB3A 1k Units Tape and Reel MUA08A

LMV652MMX 3.5k Units Tape and Reel

14-Pin TSSOP LMV654MT LMV654MT 94 Units/Rail MTC14

LMV654MTX 2.5k Units Tape and Reel

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LMV651/LMV652/LMV654

Typical Performance Characteristics Unless otherwise specified, TA= 25°C, VS= 5V, V+= 5V, V−= 0V,

VCM= VS/2

Supply Current vs. Supply Voltage (LMV651)

20123834

Supply Current per Channel vs. Supply Voltage (LMV652)

20123865

Supply Current per Channel vs. Supply Voltage (LMV654)

20123864

VOS vs. VCM

20123825

VOS vs. VCM

20123826

VOS vs. Supply Voltage

20123821

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LMV651/LMV652/LMV654

IBIAS vs. VCM

20123823

IBIAS vs. VCM

20123824

IBIAS vs. Supply Voltage

20123822

Positive Output Swing vs. Supply Voltage

20123828

Negative Output Swing vs. Supply Voltage

20123829

Positive Output Swing vs. Supply Voltage

20123827

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LMV651/LMV652/LMV654

Negative Output Swing vs. Supply Voltage

20123830

Sourcing Current vs. Output Voltage

20123832

Sinking Current vs. Output Voltage (LMV651)

20123833

Sinking Current vs. Output Voltage (LMV652)

20123866

Sinking Current vs. Output Voltage (LMV654)

20123863

Open Loop Gain and Phase with Capacitive Load

20123811

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LMV651/LMV652/LMV654

Open Loop Gain and Phase with Resistive Load

20123812

Phase Margin vs. Capacitive Load (Stability)

20123813

Input Referred Voltage Noise vs. Frequency

20123814

Input Referred Current Noise vs. Frequency

20123815

Slew Rate vs. Supply Voltage

20123816

THD+N vs. VOUT

20123809

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LMV651/LMV652/LMV654

THD+N vs. VOUT

20123810

THD+N vs. Frequency

20123807

THD+N vs. Frequency

20123808

Small Signal Transient Response

20123818

Small Signal Transient Response

20123817

Large Signal Transient Response

20123819

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LMV651/LMV652/LMV654

PSRR vs. Frequency

20123835

CMRR vs. Frequency

20123836

Closed Loop Output Impedance vs. Frequency

20123837

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LMV651/LMV652/LMV654

Application Information

ADVANTAGES OF THE LMV651/LMV652/LMV654

Low Voltage and Low Power Operation

The LMV651/LMV652/LMV654 have performance guaran-

teed at supply voltages of 3V and 5V. These parts are guar-

anteed to be operational at all supply voltages between 2.7V

and 5.5V. The LMV651 draws a low supply current of 116

μA, the LMV652 draws 118 μA/channel and the LMV654

draws 122 μA/channel. This family of op amps provides the

low voltage and low power amplification which is essential for

portable applications.

Wide Bandwidth

Despite drawing the very low supply current of 116 µA, the

LMV651/LMV652/LMV654 manage to provide a wide unity

gain bandwidth of 12 MHz. This is easily one of the best

bandwidth to power ratios ever achieved, and allows these op

amps to provide wideband amplification while using the min-

imum amount of power. This makes this family of parts ideal

for low power signal processing applications such as portable

media players and other accessories.

Low Input Referred Noise

The LMV651/LMV652/LMV654 provide a flatband input re-

ferred voltage noise density of 17 nV/ , which is signifi-

cantly better than the noise performance expected from a low

power op amp. These op amps also feature exceptionally low

1/f noise, with a very low 1/f noise corner frequency of 4 Hz.

This makes these parts ideal for low power applications which

require decent noise performance, such as PDAs and

portable sensors.

Ground Sensing and Rail-to-Rail Output

The LMV651/LMV652/LMV654 each have a rail-to-rail output

stage, which provides the maximum possible output dynamic

range. This is especially important for applications requiring

a large output swing. The input common mode range of this

family of devices includes the negative supply rail which al-

lows direct sensing at ground in a single supply operation.

Small Size

The small footprint of the packages for the LMV651/LMV652/

LMH654 saves space on printed circuit boards, and enables

the design of smaller and more compact electronic products.

Long traces between the signal source and the op amp make

the signal path susceptible to noise. By using a physically

smaller package, these op amps can be placed closer to the

signal source, reducing noise pickup and enhancing signal

integrity.

STABILITY OF OP AMP CIRCUITS

Stability and Capacitive Loading

If the phase margin of the LMV651/LMV652/LMV654 is plot-

ted with respect to the capacitive load (CL) at its output, it is

seen that the phase margin reduces significantly if CL is in-

creased beyond 100 pF. This is because the op amp is

designed to provide the maximum bandwidth possible for a

low supply current. Stabilizing it for higher capacitive loads

would have required either a drastic increase in supply cur-

rent, or a large internal compensation capacitance, which

would have reduced the bandwidth of the op amp. Hence, if

these devices are to be used for driving higher capacitive

loads, they would have to be externally compensated.

20123859

FIGURE 1. Gain vs. Frequency for an Op Amp

An op amp, ideally, has a dominant pole close to DC, which

causes its gain to decay at the rate of 20 dB/decade with re-

spect to frequency. If this rate of decay, also known as the

rate of closure (ROC), remains the same until the op amp's

unity gain bandwidth, the op amp is stable. If, however, a large

capacitance is added to the output of the op amp, it combines

with the output impedance of the op amp to create another

pole in its frequency response before its unity gain frequency

(Figure 1). This increases the ROC to 40 dB/decade and

causes instability.

In such a case a number of techniques can be used to restore

stability to the circuit. The idea behind all these schemes is to

modify the frequency response such that it can be restored to

an ROC of 20 dB/decade, which ensures stability.

In The Loop Compensation

Figure 2 illustrates a compensation technique, known as ‘in

the loop’ compensation, that employs an RC feedback circuit

within the feedback loop to stabilize a non-inverting amplifier

configuration. A small series resistance, RS, is used to isolate

the amplifier output from the load capacitance, CL, and a small

capacitance, CF, is inserted across the feedback resistor to

bypass CL at higher frequencies.

20123858

FIGURE 2. In the Loop Compensation

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LMV651/LMV652/LMV654

The values for RS and CF are decided by ensuring that the

zero attributed to CF lies at the same frequency as the pole

attributed to CL. This ensures that the effect of the second

pole on the transfer function is compensated for by the pres-

ence of the zero, and that the ROC is maintained at 20 dB/

decade. For the circuit shown in Figure 2 the values of RS and

CF are given by Equation 1. Values of RS and CF required for

maintaining stability for different values of CL, as well as the

phase margins obtained, are shown in Table 1. RF and RIN

are taken to be 10 kΩ, RL is 2 kΩ, while ROUT is taken as

340Ω.

(1)

TABLE 1.

CL (pF) RS (Ω) CF (pF) Phase Margin (°)

150 340 15 39.4

200 340 20 34.6

250 340 25 31.1

Although this methodology provides circuit stability for any

load capacitance, it does so at the price of bandwidth. The

closed loop bandwidth of the circuit is now limited by RF and

CF.

Compensation By External Resistor

In some applications it is essential to drive a capacitive load

without sacrificing bandwidth. In such a case, in the loop com-

pensation is not viable. A simpler scheme for compensation

is shown in Figure 3. A resistor, RISO, is placed in series be-

tween the load capacitance and the output. This introduces a

zero in the circuit transfer function, which counteracts the ef-

fect of the pole formed by the load capacitance, and ensures

stability. The value of RISO to be used should be decided de-

pending on the size of CL and the level of performance de-

sired. Values ranging from 5Ω to 50Ω are usually sufficient to

ensure stability. A larger value of RISO will result in a system

with lesser ringing and overshoot, but will also limit the output

swing and the short circuit current of the circuit.

20123860

FIGURE 3. Compensation by Isolation Resistor

Typical Applications

HIGH GAIN LOW POWER AMPLIFIERS

With a low supply current, low power operation, and low har-

monic distortion, the LMV651/LMV652/LMV654 are ideal for

wide-bandwidth, high gain amplification. The wide unity gain

bandwidth allows these parts to provide large gain over a wide

frequency range, while driving loads as low as 2 kΩ with less

than 0.003% distortion. Two amplifier circuits are shown in

Figure 4 and Figure 5. Figure 4 is an inverting amplifier, with

a 100 kΩ feedback resistor, R2, and a 1 kΩ input resistor,

R1, and provides a gain of −100. With the LMV651/LMV652/

LMV654 these circuits can provide gain of −100 with a −3 dB

bandwidth of 120 kHz, for a quiescent current as low as 116

μA. Similarly, the circuit in Figure 5, a non-inverting amplifier

with a gain of 1001, can provide that gain with a −3 dB band-

width of 12 kHz, for a similar low quiescent power dissipation.

Coupling capacitors CC1 and CC2 can be added to isolate the

circuit from DC voltages, while RB1 and RB2 provide DC bias-

ing. A feedback capacitor CF can also be added to improve

compensation.

20123861

FIGURE 4. High Gain Inverting Amplifier

20123862

FIGURE 5. High Gain Non-Inverting Amplifier

ACTIVE FILTERS

With a wide unity gain bandwidth of 12 MHz, low input referred

noise density and a low power supply current, the LMV651/

LMV652/LMV654 are well suited for low-power filtering appli-

cations. Active filter topologies, like the Sallen-Key low pass

filter shown in Figure 6, are very versatile, and can be used

to design a wide variety of filters (Chebyshev, Butterworth or

Bessel). The Sallen-Key topology, in particular, can be used

to attain a wide range of Q, by using positive feedback to re-

ject the undesired frequency range.

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LMV651/LMV652/LMV654

In the circuit shown in Figure 6, the two capacitors appear as

open circuits at lower frequencies and the signal is simply

buffered to the output. At high frequencies the capacitors ap-

pear as short circuits and the signal is shunted to ground by

one of the capacitors before it can be amplified. Near the cut-

off frequency, where the impedance of the capacitances is on

the same order as Rg and Rf, positive feedback through the

other capacitor allows the circuit to attain the desired Q. The

ratio of the two resistors, m2, provides a knob to control the

value of Q obtained.

20123820

FIGURE 6. Sallen-Key Low Pass Filter

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LMV651/LMV652/LMV654

Physical Dimensions inches (millimeters) unless otherwise noted

5-Pin SC70

NS Package Number MAA05A

5-Pin SOT-23

NS Package Number MF05A

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LMV651/LMV652/LMV654

8-Pin MSOP

NS Package Number MUA08A

14-Pin TSSOP

NS Package Number MTC14

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LMV651/LMV652/LMV654

Notes

LMV651/LMV652/LMV654 12 MHz, Low Voltage, Low Power Amplifiers

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specifications. Buyers acknowledge and agree that any such use of TI products which TI has not designated as military-grade is solely at

the Buyer's risk, and that they are solely responsible for compliance with all legal and regulatory requirements in connection with such use.

TI products are neither designed nor intended for use in automotive applications or environments unless the specific TI products are

designated by TI as compliant with ISO/TS 16949 requirements. Buyers acknowledge and agree that, if they use any non-designated

products in automotive applications, TI will not be responsible for any failure to meet such requirements.

Following are URLs where you can obtain information on other Texas Instruments products and application solutions:

Products Applications

Audio www.ti.com/audio Communications and Telecom www.ti.com/communications

Amplifiers amplifier.ti.com Computers and Peripherals www.ti.com/computers

Data Converters dataconverter.ti.com Consumer Electronics www.ti.com/consumer-apps

DLP®Products www.dlp.com Energy and Lighting www.ti.com/energy

DSP dsp.ti.com Industrial www.ti.com/industrial

Clocks and Timers www.ti.com/clocks Medical www.ti.com/medical

Interface interface.ti.com Security www.ti.com/security

Logic logic.ti.com Space, Avionics and Defense www.ti.com/space-avionics-defense

Power Mgmt power.ti.com Transportation and Automotive www.ti.com/automotive

Microcontrollers microcontroller.ti.com Video and Imaging www.ti.com/video

RFID www.ti-rfid.com

OMAP Mobile Processors www.ti.com/omap

Wireless Connectivity www.ti.com/wirelessconnectivity

TI E2E Community Home Page e2e.ti.com

Mailing Address: Texas Instruments, Post Office Box 655303, Dallas, Texas 75265