ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
Dual Channel 14-/12-Bit, 250-/210-MSPS ADC With DDR LVDS and Parallel CMOS Outputs
Check for Samples: ADS62P49 / ADS62P29,ADS62P48 / ADS62P28
1FEATURES • Supports Input Clock Amplitude Down to 400
mVPP Differential
• Maximum Sample Rate: 250 MSPS • Internal and External Reference Support
• 14-Bit Resolution – ADS62P49/ADS62P48 • 64-QFN Package (9 mm × 9 mm)
• 12-Bit Resolution – ADS62P29/ADS62P28
• Total Power: 1.25 W at 250 MSPS ADS62Pxx High Speed Family
• Double Data Rate (DDR) LVDS and Parallel 250 MSPS 210 MSPS 200 MSPS
CMOS Output Options 14-Bit Family ADS62P49 ADS62P48
• Programmable Gain up to 6dB for SNR/SFDR 12-Bit Family ADS62P29 ADS62P28
Trade-Off 11-Bit Family ADS62C17
• DC Offset Correction
• 90dB Cross-Talk
DESCRIPTION
The ADS62Px9/x8 is a family of dual channel 14-bit and 12-bit A/D converters with sampling rates up to 250
MSPS. It combines high dynamic performance and low power consumption in a compact 64 QFN package. This
makes it well-suited for multi-carrier, wide band-width communications applications.
The ADS62Px9/x8 has gain options that can be used to improve SFDR performance at lower full-scale input
ranges. It includes a dc offset correction loop that can be used to cancel the ADC offset. Both DDR LVDS
(Double Data Rate) and parallel CMOS digital output interfaces are available.
It includes internal references while the traditional reference pins and associated decoupling capacitors have
been eliminated. Nevertheless, the device can also be driven with an external reference. The device is specified
over the industrial temperature range (–40°C to 85°C).
Table 1. Performance Summary
AT 170MHZ INPUT ADS62P49 ADS62P48 ADS62P29 ADS62P28
0 dB gain 75 78 75 78
SFDR, dBc 6 dB gain 82 84 82 84
0 dB gain 69.8 70.1 68.3 68.7
SINAD, dBFS 6 dB gain 66.5 66.3 65.8 65.8
Analog Power, W 1 0.92 1 0.92
1Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
PRODUCTION DATA information is current as of publication date. Copyright © 2009–2011, Texas Instruments Incorporated
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
INA_P
INA_M
CLKP
CLKM
VCM
SCLK
SEN
SDATA
CLOCKGEN
AVDD
AGND
DRVDD
DRGND
INB_P
INB_M
RESET
CTRL1
CTRL2
CTRL3
CLKOUTP/M
LVDS INTERFACE
ADS62P49/48
DA0_P/M
DA2_P/M
DA4_P/M
DA6_P/M
DA8_P/M
DA10_P/M
DA12_P/M
DB0_P/M
DB2_P/M
DB4_P/M
DB6_P/M
DB8_P/M
DB10_P/M
DB12_P/M
SDOUT
Output
Clock
Buffer
Sample
and
Hold
Sample
and
Hold
14-Bit
ADC
14-Bit
ADC
Digital
and
DDR
Serializer
Digital
and
DDR
Serializer
Reference ControlInterface
B0349-01
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
Figure 1. ADS62P49/48 Block Diagram
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INA_P
INA_M
CLKP
CLKM
VCM
SCLK
SEN
SDATA
CLOCKGEN
AVDD
AGND
DRVDD
DRGND
INB_P
INB_M
RESET
CTRL1
CTRL2
CTRL3
CLKOUTP/M
LVDS INTERFACE
ADS62P29/28
DA0_P/M
DA2_P/M
DA4_P/M
DA6_P/M
DA8_P/M
DA10_P/M
DB0_P/M
DB2_P/M
DB4_P/M
DB6_P/M
DB8_P/M
DB10_P/M
SDOUT
Output
Clock
Buffer
Sample
and
Hold
Sample
and
Hold
12-Bit
ADC
12-Bit
ADC
Digital
and
DDR
Serializer
Digital
and
DDR
Serializer
Reference ControlInterface
B0350-01
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
Figure 2. ADS62P29/28 Block Diagram
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Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
PACKAGE/ORDERING INFORMATION(1)
SPECIFIED
PACKAGE- PACKAGE ECO LEAD/BALL PACKAGE ORDERING TRANSPORT
PRODUCT TEMPERATURE
LEAD DESIGNATOR PLAN(2) FINISH MARKING NUMBER MEDIA,QUANTITY
RANGE
ADS62P49IRGCT,
ADS62P49 AZ62P49 ADS62P49IRGCR Tape and Reel
ADS62P48IRGCT,
ADS62P48 AZ62P48
GREEN ADS62P48IRGCR
QFN-64 RGC –40°C to 85°C (RoHS and Cu NiPdAu ADS62P29IRGCT,
no Sb/Br)
ADS62P29 AZ62P29 ADS62P29IRGCR Tape and Reel
ADS62P28IRGCT,
ADS62P28 AZ62P28 ADS62P28IRGCR
(1) For the most current product and ordering information, see the Package Option Addendum at the end of this document, or see the TI
web site at www.ti.com.
(2) Eco Plan – The planned eco-friendly classification: Green (RoHS and no Sb/Br): TI defines “Green” to mean Pb-Free (RoHS compatible)
and free of Bromine (Br) and Antimony (Sb) based flame retardants.
ABSOLUTE MAXIMUM RATINGS(1)
over operating free-air temperature range (unless otherwise noted) VALUE UNIT
Supply voltage range, AVDD –0.3 V to 3.9 V
Supply voltage range, DRVDD –0.3 V to 2.2 V
Voltage between AGND and DRGND –0.3 to 0.3 V
Voltage between AVDD to DRVDD (AVDD leads DRVDD during power –0.3 to 4.2 V
up/DRVDD leads AVDD during power down)
Voltage between DRVDD to AVDD (DRVDD leads AVDD during power –2.5 to 1.7 V
up/AVDD leads DRVDD during power down)
Voltage applied to external pin, VCM (in external reference mode) –0.3 to 2.0 V
Voltage applied to analog input pins – INP_A, INM_A, INP_B, INM_B –0.3V to minimum ( 3.6, AVDD + 0.3V ) V
Voltage applied to input pins - CLKP, CLKM(2), RESET, SCLK, SDATA, –0.3V to AVDD + 0.3V V
SEN, CTRL1, CTRL2, CTRL3
TAOperating free-air temperature range –40 to 85 °C
TJOperating junction temperature range 125 °C
Tstg Storage temperature range –65 to 150 °C
ESD, human body model 2 kV
(1) Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings
only and functional operation of the device at these or any other conditions beyond those indicated under recommended operating
conditions is not implied. Exposure to absolute maximum rated conditions for extended periods may affect device reliability.
(2) When AVDD is turned off, it is recommended to switch off the input clock (or ensure the voltage on CLKP, CLKM is < |0.3V|). This
prevents the ESD protection diodes at the clock input pins from turning on.
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ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
THERMAL INFORMATION ADS62Pxx
THERMAL METRIC(1) RGC PACKAGE UNITS
64 PINS
qJA Junction-to-ambient thermal resistance(2) 23.0
qJCtop Junction-to-case (top) thermal resistance(3) 10.5
qJB Junction-to-board thermal resistance(4) 4.2 °C/W
yJT Junction-to-top characterization parameter(5) 0.1
yJB Junction-to-board characterization parameter(6) 4.2
qJCbot Junction-to-case (bottom) thermal resistance(7) 0.57
(1) For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
(2) The junction-to-ambient thermal resistance under natural convection is obtained in a simulation on a JEDEC-standard, high-K board, as
specified in JESD51-7, in an environment described in JESD51-2a.
(3) The junction-to-case (top) thermal resistance is obtained by simulating a cold plate test on the package top. No specific
JEDEC-standard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
(4) The junction-to-board thermal resistance is obtained by simulating in an environment with a ring cold plate fixture to control the PCB
temperature, as described in JESD51-8.
(5) The junction-to-top characterization parameter, yJT, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining qJA, using a procedure described in JESD51-2a (sections 6 and 7).
(6) The junction-to-board characterization parameter, yJB, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining qJA , using a procedure described in JESD51-2a (sections 6 and 7).
(7) The junction-to-case (bottom) thermal resistance is obtained by simulating a cold plate test on the exposed (power) pad. No specific
JEDEC standard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
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Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
Vpp
Vp
0
V - V
CLKP CLKM
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
RECOMMENDED OPERATING CONDITIONS MIN TYP MAX UNIT
SUPPLIES
AVDD Analog supply voltage 3.15 3.3 3.6 V
DRVDD Digital supply voltage 1.7 1.8 1.9 V
ANALOG INPUTS
Differential input voltage range 2 VPP
Input common-mode voltage 1.5 ±0.1 V
Voltage applied on CM in external reference mode 1.5±0.05 V
Maximum analog input frequency with 2 Vpp input amplitude(1) 500 MHz
Maximum analog input frequency with 1 Vpp input amplitude(1) 800 MHz
CLOCK INPUT
Input clock sample rate Enable low speed mode(2) 1 80
ADS62P49 / ADS62P29 MSPS
Low speed mode disabled (default mode after reset) >80 250(3)
Enable low speed mode(2) 1 80
ADS62P48 / ADS62P28 MSPS
Low speed mode disabled (default mode after reset) >80 210
With multiplexed mode enabled(4) 1 65 MSPS
Input clock amplitude differential (VCLKP–VCLKM)(5)(6)
Sine wave, ac-coupled 0.2 1.5 VPP
LVPECL, ac-coupled 1.6 VPP
LVDS, ac-coupled 0.7 VPP
LVCMOS, single-ended, ac-coupled 3.3 V
Input clock duty cycle 40% 50% 60%
DIGITAL OUTPUTS
CLOAD Maximum external load capacitance from each output pin to DRGND 5 pF
RLOAD Differential load resistance between the LVDS output pairs (LVDS mode) 100 Ω
TAOperating free-air temperature –40 85 °C
(1) See the Theory of Operation section for information.
(2) Use register bit <ENABLE LOW SPEED MODE>, refer to the Serial Register Map section for information.
(3) With LVDS interface only; maximum recommended sample rate with CMOS interface is 210 MSPS.
(4) See the Multiplexed Output Mode section for information.
(5) Refer to Performance vs Input Clock Amplitude Chart on Figure 35,Figure 52,Figure 69, and Figure 86.
(6) Refer to Figure 3 for the definition of clock amplitude.
Figure 3. Clock Amplitude Definition Diagram
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ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
ELECTRICAL CHARACTERISTICS – ADS62P49/48 and ADS62P29/28
Typical values are at 25°C, AVDD = 3.3V, DRVDD = 1.8V, 50% clock duty cycle, –1dBFS differential analog input, internal
reference mode (unless otherwise noted).
Min and max values are across the full temperature range TMIN = –40°C to TMAX = 85°C, AVDD = 3.3V, DRVDD = 1.8V
ADS62P49/ADS62P29 ADS62P48/ADS62P28
250 MSPS 210 MSPS
PARAMETER UNIT
MIN TYP MAX MIN TYP MAX
ANALOG INPUT
Differential input voltage range (0 dB gain) 2 2 Vpp
Differential input resistance (at dc), See Figure 100 > 1 > 1 MΩ
Differential input capacitance, See Figure 101 3.5 3.5 pF
Analog input bandwidth (with 25Ωsource impedance) 700 700 MHz
Analog Input common mode current (per channel) 3.6 3.6 mA/MSPS
VCM Common mode output voltage 1.5 1.5 V
VCM Output current capability ±4 ±4 mA
DC ACCURACY
Offset error –20 ±2 20 –20 ±2 20 mV
Temperature coefficient of offset error 0.02 0.02 mV/ °C
Variation of offset error with supply 0.5 0.5 mV/V
There are two sources of gain error – internal reference
inaccuracy and channel gain error.
EGREF Gain error due to internal reference inaccuracy alone –1 ±0.2 1 –1 ±0.2 1 % FS
EGCHAN Gain error of channel alone(1) –1 ±0.2 1 –1 ±0.2 1 % FS
Temperature coefficient of EGCHAN 0.002 0.002 Δ% /°C
Difference in gain errors between two channels –2 2 –2 2
Gain within the same device
matching % FS
Difference in gain errors between two channels
(2) –4 4 –4 4
across two devices
POWER SUPPLY
IAVDD Analog supply current 305 350 280 320 mA
Output buffer supply current, LVDS interface with 100 Ω
IDRVDD 133 175 122 165 mA
external termination
Output buffer supply current, CMOS interface, Fin = 2MHz,
IDRVDD – 91 mA
No external load capacitance (3) (4)
Analog power 1.01 1.15 0.92 1.05 W
Digital power, LVDS interface 0.24 0.315 0.22 0.3 W
Global power down 45 100 45 100 mW
(1) This is specified by design and characterization; it is not tested in production.
(2) For two channels within the same device, only the channel gain error matters, as the reference is common for both channels.
(3) In CMOS mode, the DRVDD current scales with the sampling frequency, the load capacitance on output pins, input frequency and the
supply voltage (see Figure 92 and CMOS interface power dissipation in application section).
(4) The maximum DRVDD current with CMOS interface depends on the actual load capacitance on the digital output lines. Note that the
maximum recommended load capacitance on each digital output line is 10 pF.
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ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
ELECTRICAL CHARACTERISTICS – ADS62P49/48
Typical values are at 25°C, AVDD = 3.3V, DRVDD = 1.8V, 50% clock duty cycle, –1dBFS differential analog input, 0 dB gain,
internal reference mode (unless otherwise noted).
Min and max values are across the full temperature range TMIN = –40°C to TMAX = 85°C, AVDD = 3.3V, DRVDD = 1.8V
ADS62P49 ADS62P48
250 MSPS 210 MSPS
PARAMETER TEST CONDITIONS UNIT
MIN TYP MAX MIN TYP MAX
Fin= 20 MHz 73.4 73.4
Fin = 60 MHz 73 73
SNR Fin = 100 MHz 72 72
Signal to noise ratio, dBFS
0 dB gain 68 71 68 71
LVDS Fin = 170 MHz 6 dB gain 66.6 66.4
Fin = 230 MHz 69.8 69.7
Fin= 20 MHz 73.2 73
Fin = 60 MHz 72.7 72.8
SINAD Fin = 100 MHz 71.2 71.5
Signal to noise and distortion ratio, dBFS
0 dB gain 66.5 69.8 66.5 70.1
LVDS Fin = 170 MHz 6 dB gain 66.5 66.3
Fin = 230 MHz 69 68
ENOB, Fin = 170 MHz 11.3 11.4 LSB
Effective number of bits
DNL Fin = 170 MHz –0.95 ±0.6 1.3 –0.95 ±0.6 1.3 LSB
Differential non-linearity
INL Fin = 170 MHz –5 ±2.5 5 –5 ±2.5 5 LSB
Integrated non-linearity
ELECTRICAL CHARACTERISTICS – ADS62P29/28
Typical values are at 25°C, AVDD = 3.3V, DRVDD = 1.8V, 50% clock duty cycle, –1dBFS differential analog input, 0 dB gain,
internal reference mode (unless otherwise noted).
Min and max values are across the full temperature range TMIN = –40°C to TMAX = 85°C, AVDD = 3.3V, DRVDD = 1.8V
ADS62P29 ADS62P28
250 MSPS 210 MSPS
PARAMETER TEST CONDITIONS UNIT
MIN TYP MAX MIN TYP MAX
Fin= 20 MHz 70.7 70.8
Fin = 60 MHz 70.5 70.6
SNR Fin = 100 MHz 69.8 70
Signal to noise ratio, dBFS
0 dB gain 66.5 69.4 66.5 69.4
LVDS Fin = 170 MHz 6 dB gain 66 65.9
Fin = 230 MHz 68.4 68.4
Fin= 20 MHz 70.6 70.6
Fin = 60 MHz 70.3 70.5
SINAD Fin = 100 MHz 69.3 69.7
Signal to noise and distortion ratio, dBFS
0 dB gain 66 68.3 66 68.7
LVDS Fin = 170 MHz 6 dB gain 65.9 65.8
Fin = 230 MHz 67.9 67.1
ENOB, Fin = 170 MHz 11 11.1 LSB
Effective number of bits
DNL –0.9 ±0.2 1.3 –0.9 ±0.2 1.3 LSB
Differential non-linearity
INL –5 ±1 5 –5 ±1 5 LSB
Integrated non-linearity
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ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
ELECTRICAL CHARACTERISTICS – ADS62P49/48
Typical values are at 25°C, AVDD = 3.3V, DRVDD = 1.8V, 50% clock duty cycle, –1dBFS differential analog input, 0 dB gain,
internal reference mode (unless otherwise noted).
Min and max values are across the full temperature range TMIN = –40°C to TMAX = 85°C, AVDD = 3.3V, DRVDD = 1.8V
ADS62P49/ADS62P29 ADS62P48/ADS62P28
250 MSPS 210 MSPS
PARAMETER TEST CONDITIONS UNIT
MIN TYP MAX MIN TYP MAX
Fin= 20 MHz 89 85
Fin = 60 MHz 85 85
SFDR Fin = 100 MHz 78 80 dBc
Spurious Free Dynamic Range Fin = 170 MHz 71 75 71 77
Fin = 230 MHz 77 72
Fin= 20 MHz 98 98
Fin = 60 MHz 95 95
SFDR
Spurious Free Dynamic Range, Fin = 100 MHz 92 92 dBc
excluding HD2,HD3 Fin = 170 MHz 77 90 78 91
Fin = 230 MHz 90 90
Fin= 20 MHz 93 95
Fin = 60 MHz 90 94
HD2 Fin = 100 MHz 90 90 dBc
Second Harmonic Distortion Fin = 170 MHz 71 85 71 88
Fin = 230 MHz 85 80
Fin= 20 MHz 89 85
Fin = 60 MHz 85 85
HD3 Fin = 100 MHz 78 80 dBc
Third Harmonic Distortion Fin = 170 MHz 71 75 71 77
Fin = 230 MHz 77 72
Fin= 20 MHz 87 83.5
Fin = 60 MHz 83.5 84.6
THD Fin = 100 MHz 77.5 79.7 dBc
Total harmonic distortion Fin = 170 MHz 70 74 70.5 76.5
Fin = 230 MHz 75 71
F1 = 46 MHz, F2 = 50 MHz, 87 91
each tone at –7 dBFS
IMD dBFS
F1 = 185 MHz, F2 = 190
2-Tone Inter-modulation Distortion MHz, 85 84.5
each tone at –7 dBFS
Up to 200-MHz cross-talk
Cross-talk 90 90 dB
frequency
Recovery to within 1% (of final Clock
Input overload recovery value) for 6-dB overload with 1 1 Cycles
sine wave input
PSRR For 100-mV pp signal on 25 25 dB
AC Power supply rejection ratio AVDD supply
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Dn_Dn+1_P
DAnP/DBnP
Dn_Dn+1_M
DAnM/DBnM
GND
GND
V
VOCM
Logic0
V = –350mV
ODL
(1)
Logic1
V =350mV
ODH
(1)
T0334-02
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
DIGITAL CHARACTERISTICS — ADS62Px9/x8
The DC specifications refer to the condition where the digital outputs are not switching, but are permanently at a valid logic
level 0 or 1. AVDD = 3.3V, DRVDD = 1.8V ADS62P49/ADS62P48/
ADS62P29/ADS62P28
PARAMETER TEST CONDITIONS UNIT
MIN TYP MAX
DIGITAL INPUTS – CTRL1, CTRL2, CTRL3, RESET, SCLK, SDATA, SEN(1)
High-level input voltage 1.3 V
All digital inputs support 1.8V and 3.3V
CMOS logic levels.
Low-level input voltage 0.4 V
SDATA, SCLK(2) 16
High-level input current VHIGH = 3.3 V mA
SEN(3) 10
SDATA, SCLK 0
Low-level input current VLOW = 0 V mA
SEN –20
Input capacitance 4 pF
DIGITAL OUTPUTS – CMOS INTERFACE (DA0-DA13, DB0-DB13, CLKOUT, SDOUT)
High-level output voltage DRVDD
IOH = 1mA DRVDD V
–0.1
Low-level output voltage IOL = 1mA 0 0.1 V
Output capacitance (internal to device) 2 pF
DIGITAL OUTPUTS – LVDS INTERFACE
VODH High-level output differential voltage With external 100 Ωtermination. 275 350 425 mV
VODL Low-level output differential voltage With external 100 Ωtermination. –425 –350 –275 mV
VOCM Output common-mode voltage 1 1.15 1.4 V
Capacitance inside the device from
Output Capacitance 2 pF
each output to ground
(1) SCLK, SDATA, SEN function as digital input pins in serial configuration mode.
(2) SDATA, SCLK, RESET, CTRL1, CTRL2, and CTRL3 have an internal 100-kΩpull-down resistor.
(3) SEN has internal 100 kΩpull-up resistor to AVDD. Since the pull-up is weak, SEN can also be driven by 1.8V or 3.3V CMOS buffers.
(1) With external 100-Ωtermination
Figure 4. LVDS Output Voltage Levels
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SLAS635B –APRIL 2009–REVISED JANUARY 2011
TIMING REQUIREMENTS – LVDS AND CMOS MODES(1)
Typical values are at 25°C, AVDD = 3.3V, DRVDD = 1.8V, sampling frequency = 250 MSPS, sine wave input clock, 1.5 Vpp
clock amplitude, CLOAD = 5pF(2) , RLOAD = 100Ω(3) , (unless otherwise noted).
Min and max values are across the full temperature range TMIN = –40°C to TMAX = 85°C, AVDD = 3.3V, DRVDD = 1.7V to
1.9V PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
taAperture delay 0.7 1.2 1.7 ns
Aperture delay matching Between two channels within the same device ±50 ps
tjAperture jitter 145 fs rms
Time to valid data after coming out of STANDBY mode 1 3 ms
Time to valid data after coming out of global powerdown 20 50 ms
Wake-up time Time to valid data after stopping and restarting the input clock 10 Clock
cycles
Clock
ADC latency(4) 22 cycles
DDR LVDS MODE(5)
tsu Data setup time Data valid(6) to zero-crossing of CLKOUTP 0.55 0.9 ns
thData hold time Zero-crossing of CLKOUTP to data becoming invalid(6) 0.55 0.95 ns
tPDI Input clock falling edge cross-over to output clock rising edge t PDI = 0.69×Ts + tdelay
cross-over
Clock propagation delay 100 MSPS ≤Sampling frequency ≤250 MSPS
tdelay 4.2 5.7 7.2 ns
Ts = 1/Sampling frequency
Difference in tdelay between two devices operating at same
tdelay skew ±500 ps
temperature and DRVDD supply voltage
Duty cycle of differential clock, (CLKOUTP-CLKOUTM)
LVDS bit clock duty cycle 52%
100 MSPS ≤Sampling frequency ≤250 MSPS
Rise time measured from –100mV to +100mV
tRISE, Data rise time, Fall time measured from +100mV to –100mV 0.14 ns
tFALL Data fall time 1MSPS ≤Sampling frequency ≤250 MSPS
Rise time measured from –100mV to +100mV
tCLKRISE, Output clock rise time, Fall time measured from +100mV to –100mV 0.14 ns
tCLKFALL Output clock fall time 1 MSPS ≤Sampling frequency ≤250 MSPS
Output buffer enable to
tOE Time to valid data after output buffer becomes active 100 ns
data delay
PARALLEL CMOS MODE(7) at Fs = 210 MSPS
tSTART Input clock to data delay Input clock falling edge cross-over to start of data valid(8) 2.5 ns
tDV Data valid time Time interval of valid data(8) 1.7 2.7 ns
tPDI Input clock falling edge cross-over to output clock rising edge tPDI = 0.28 × Ts + tdelay
cross-over
Clock propagation delay 100 MSPS ≤Sampling frequency ≤150 MSPS
tdelay 5.5 7.0 8.5 ns
Ts = 1/Sampling frequency
Duty cycle of output clock, CLKOUT
Output clock duty cycle 43%
100 MSPS ≤Sampling frequency ≤150 MSPS
Rise time measured from 20% to 80% of DRVDD
tRISE, Data rise time, Fall time measured from 80% to 20% of DRVDD 1.2 ns
tFALL Data fall time 1≤Sampling frequency ≤210 MSPS
Rise time measured from 20% to 80% of DRVDD
tCLKRISE, Output clock rise time, Fall time measured from 80% to 20% of DRVDD 0.8 ns
tCLKFALL Output clock fall time 1≤Sampling frequency ≤150 MSPS
(1) Timing parameters are ensured by design and characterization and not tested in production
(2) CLOAD is the effective external single-ended load capacitance between each output pin and ground
(3) RLOAD is the differential load resistance between the LVDS output pair.
(4) At higher clock frequencies, tPDI is greater than one clock period and overall latency = ADC latency + 1.
(5) Measurements are done with a transmission line of 100Ωcharacteristic impedance between the device and the load. Setup and hold
time specifications take into account the effect of jitter on the output data and clock.
(6) Data valid refers to LOGIC HIGH of +100.0mV and LOGIC LOW of –100.0mV.
(7) For Fs> 150 MSPS, it is recommended to use external clock for data capture and NOT the device output clock signal (CLKOUT).
(8) Data valid refers to LOGIC HIGH of 1.26V and LOGIC LOW of 0.54V.
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TIMING REQUIREMENTS – LVDS AND CMOS MODES(1) (continued)
Typical values are at 25°C, AVDD = 3.3V, DRVDD = 1.8V, sampling frequency = 250 MSPS, sine wave input clock, 1.5 Vpp
clock amplitude, CLOAD = 5pF(2) , RLOAD = 100Ω(3) , (unless otherwise noted).
Min and max values are across the full temperature range TMIN = –40°C to TMAX = 85°C, AVDD = 3.3V, DRVDD = 1.7V to
1.9V PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
Output buffer enable (OE)
tOE Time to valid data after output buffer becomes active 100 ns
to data delay (9)
(9) Output buffer enable is controlled by Serial Interface Register 0x40. The output buffer becomes active once serial control data for output
buffer is latched in on the 16th SCLK falling edge when SEN is low.
Table 2. LVDS Timings at Lower Sampling Frequencies
Setup Time, ns Hold Time, ns
Sampling Frequency, MSPS MIN TYP MAX MIN TYP MAX
210 0.75 1.1 0.75 1.15
185 0.9 1.25 0.85 1.25
153 1.15 1.55 1.1 1.5
125 1.6 2 1.45 1.85
< 100 2 2
(Enable LOW SPEED mode for Fs ≤80) (1)
tPDI, ns
1≤Fs ≤100 MIN TYP MAX
(Enable LOW SPEED mode for Fs ≤80) (1) 12.6
(1) LOW SPEED mode can be enabled with serial interface configuration only.
Table 3. CMOS Timings at Lower Sampling Frequencies
Timings Specified With Respect to Input Clock
Sampling Frequency, MSPS tSTART, ns Data Valid time, ns
MIN TYP MAX MIN TYP MAX
210 2.5 1.7 2.7
190 1.9 2 3
170 0.9 2.7 3.7
150 6 3.6 4.6
Timings Specified With Respect to CLKOUT
Sampling Frequency, MSPS Setup Time, ns Hold Time, ns
MIN TYP MAX MIN TYP MAX
170 2.1 3.7 0.35 1.0
150 2.8 4.4 0.5 1.2
125 3.8 5.4 0.8 1.5
<100 5 1.2
(Enable LOW SPEED mode for Fs ≤80) (1)
tPDI, ns
1≤Fs ≤100 MIN TYP MAX
Enable LOW SPEED mode for Fs ≤80) (1) 9
(1) LOW SPEED mode can be enabled with serial interface configuration only.
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T0105-11
OO O O O O O O OO
Input
Clock
CLKOUTM
CLKOUTP
OutputData
DXP,DXM
DDR
LVDS
N – 22 N – 21 N – 20 N – 19 N – 18 N – 1 NN+1 N+2
N – 22 N – 21 N – 20 N – 19 N+1
CLKOUT
OutputData
D0–D13
Parallel
CMOS
Input
Signal
Sample
N
N+1
N+2 N+3 N+4
tPDI
ta
tPDI
CLKM
CLKP
N+22
N+23 N+24
E – EvenBitsD0,D2,D4,...
O – OddBitsD1,D3,D5,... N
N – 1
22ClockCycles
22ClockCycles
E E E E E E E E EE
T0106-08
Input
Clock
Output
Clock
Output
DataPair
CLKP
CLKOUTM
DAnP/M
DBnP/M
CLKM
tPDI
th
th
tsu
tsu
CLKOUTP
Dn(1) Dn+1(2)
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SLAS635B –APRIL 2009–REVISED JANUARY 2011
Figure 5. Latency Diagram
(1) Dn - Bits D0, D2, D4, ...
(2) Dn + 1 - Bits D1, D3, D5, ...
Figure 6. LVDS Interface Timing
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T0107-07
Output
Data DAn,DBn
tSTART
Dn(1)
Input
Clock
CLKP
CLKM
Input
Clock
Output
Clock
Output
Data
CLKP
DAn,DBn
CLKM
tsu
th
CLKOUT
Dn(1)
tPDI
tDV
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(1) Dn - Bits D0, D1, D2, ... of Channel A and B
Figure 7. CMOS Interface Timing
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SLAS635B –APRIL 2009–REVISED JANUARY 2011
DEVICE CONFIGURATION
ADS62Px9/x8 can be configured independently using either parallel interface control or serial interface
programming.
PARALLEL CONFIGURATION ONLY
To put the device in parallel configuration mode, keep RESET tied to high (AVDD or DRVDD).
Now, pins SEN, SCLK, CTRL1, CTRL2 and CTRL3 can be used to directly control certain modes of the ADC.
The device can be easily configured by connecting the parallel pins to the correct voltage levels (as described in
Table 4 to Table 7). There is no need to apply reset and SDATA pin can be connected to ground.
In this mode, SEN and SCLK function as parallel interface control pins. Frequently used functions can be
controlled in this mode – power down modes, internal/external reference, selection between LVDS/CMOS
interface and output data format.
Table 4 has a brief description of the modes controlled by the four parallel pins.
Table 4. Parallel Pin Definition
PIN TYPE OF PIN CONTROLS MODES
SCLK Internal/external reference
Analog control pins (controlled by analog LVDS/CMOS interface and output data
voltage levels, see Figure 8)
SEN format
CTRL1 Digital control pins (controlled by digital logic
CTRL2 Controls power down modes
levels)
CTRL3
SERIAL INTERFACE CONFIGURATION ONLY
To exercise this mode, first the serial registers have to be reset to their default values and RESET pin has to be
kept low.
SEN, SDATA and SCLK function as serial interface pins in this mode and can be used to access the internal
registers of the ADC.
The registers can be reset either by applying a pulse on RESET pin or by setting the <RESET> bit high. The
serial interface section describes the register programming and register reset in more detail
DETAILS OF PARALLEL CONFIGURATION ONLY
The functions controlled by each parallel pin are described below. A simple way of configuring the parallel pins is
shown in Figure 8.
Table 5. SCLK CONTROL PIN
VOLTAGE APPLIED ON SCLK DESCRIPTION
0Internal reference
+200mV/-0mV
(3/8)AVDD External reference
+/- 200mV
(5/8) AVDD External reference
+/- 200mV
AVDD Internal reference
+0mV/-200mV
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ToParallelPin
GND
GND
AVDD
AVDD
(5/8) AVDD
(5/8) AVDD
3R
2R
3R
(3/8) AVDD
(3/8) AVDD
S0321-01
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Table 6. SEN CONTROL PIN
VOLTAGE APPLIED ON SEN DESCRIPTION
0 (+200mV/–0mV) 2’s complement, DDR LVDS output
(3/8)AVDD (±200mV) Offset binary, DDR LVDS output
(5/8)AVDD (±200mV) Offset binary, parallel CMOS output
AVDD (+0mV/–200mV) 2's compliment, parallel CMOS output
Table 7. CTRL1, CTRL2 and CTRL3 PINS (1)
CTRL1 CTRL2 CTRL3 DESCRIPTION
LOW LOW LOW Normal operation
LOW LOW HIGH Not available
LOW HIGH LOW Not available
LOW HIGH HIGH Not available
HIGH LOW LOW Global power down
HIGH LOW HIGH Channel B standby
HIGH HIGH LOW Channel A standby
HIGH HIGH HIGH MUX mode of operation, Channel A and B data is multiplexed and output on DA13 to DA0 pins.(2)
(1) See POWER DOWN in the APPLICATION INFORMATION section.
(2) Low Speed mode has to be enabled for Multiplexed Output mode (MUX mode). Therefore, MUX mode works with serial interface
configuration only and is not supported with parallel configuration.
Figure 8. Simple Scheme to Configure Parallel Pins
USING BOTH SERIAL INTERFACE AND PARALLEL CONTROLS
For increased flexibility, a combination of serial interface registers and parallel pin controls (CTRL1 to CTRL3)
can also be used to configure the device. To allow this, keep RESET low. The parallel interface control pins
CTRL1 to CTRL3 are available. After power-up, the device is automatically configured as per the voltage settings
on these pins (see Table 6). SEN, SDATA, and SCLK function as serial interface digital pins and are used to
access the internal registers of ADC. The registers must first be reset to their default values either by applying a
pulse on RESET pin or by setting bit <RST> = 1. After reset, the RESET pin must be kept low. The Serial
Interface section describes register programming and register reset in more detail.
SERIAL INTERFACE
The ADC has a set of internal registers, which can be accessed by the serial interface formed by pins SEN
(Serial interface Enable), SCLK (Serial Interface Clock) and SDATA (Serial Interface Data).
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T0109-01
Register Address RegisterData
t(SCLK) t(DSU)
t(DH)
t(SLOADS)
D7A7 D3A3 D5A5 D1A1 D6A6 D2A2 D4A4 D0A0
SDATA
SCLK
SEN
RESET
t(SLOADH)
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Serial shift of bits into the device is enabled when SEN is low. Serial data SDATA is latched at every falling edge
of SCLK when SEN is active (low). The serial data is loaded into the register at every 16th SCLK falling edge
when SEN is low. In case the word length exceeds a multiple of 16 bits, the excess bits are ignored. Data can be
loaded in multiple of 16-bit words within a single active SEN pulse.
The first 8 bits form the register address and the remaining 8 bits are the register data. The interface can work
with SCLK frequency from 20 MHz down to very low speeds (few Hertz) and also with non-50% SCLK duty
cycle.
Register Initialization
After power-up, the internal registers MUST be initialized to their default values. This can be done in one of two
ways:
1. Either through hardware reset by applying a high-going pulse on RESET pin (of width greater than 10ns) as
shown in Figure 9
OR
2. By applying software reset. Using the serial interface, set the <RESET> bit (D7 in register 0x00) to HIGH.
This initializes internal registers to their default values and then self-resets the <RESET> bit to low. In this
case the RESET pin is kept low.
Figure 9. Serial Interface Timing
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SERIAL INTERFACE TIMING CHARACTERISTICS
Typical values at 25°C, min and max values across the full temperature range TMIN = –40°C to TMAX = 85°C, AVDD = 3.3V,
DRVDD = 1.8V (unless otherwise noted).
PARAMETER MIN TYP MAX UNIT
fSCLK SCLK frequency (= 1/ tSCLK) > DC 20 MHz
tSLOADS SEN to SCLK setup time 25 ns
tSLOADH SCLK to SEN hold time 25 ns
tDS SDATA setup time 25 ns
tDH SDATA hold time 25 ns
Serial Register Readout
The device includes an option where the contents of the internal registers can be read back. This may be useful
as a diagnostic check to verify the serial interface communication between the external controller AND the ADC.
a. First, set register bit <SERIAL READOUT> = 1. This also disables any further writes into the registers.
b. Initiate a serial interface cycle specifying the address of the register (A7-A0) whose content has to be read.
c. The device outputs the contents (D7-D0) of the selected register on the SDOUT pin (64).
d. The external controller can latch the contents at the falling edge of SCLK.
e. To enable register writes, reset register bit <SERIAL READOUT> = 0. SDOUT is a CMOS output pin; the
readout functionality is available whether the ADC output data interface is LVDS or CMOS.
When <SERIAL READOUT> is disabled, the SDOUT pin is forced low by the device (and not put in
high-impedance). If serial readout is not used, the SDOUT pin has to be floated.
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T0386-02
D7A7 D3A3 D5A5 D1A1 D6
1010000 0
A6 D2A2 D4A4 D0A0
SDATA
SCLK
SEN
SDOUT
Register Address(A7:A0)=0x40 RegisterData(D7:D0)=XX(Don'tCare)
B)Readcontentsofregister0x40. Thisregisterhasbeeninitializedwith0x0C(deviceisputinglobalpowerdownmode)
PinSDOUT functionsasserialreadout(<SERIAL READOUT>=1)
D7A7 D3A3 D5A5 D1A1 D6A6 D2A2 D4A4 D0A0
SDATA
SCLK
SEN
SDOUT
Register Address(A7:A0)=0x00 RegisterData(D7:D0)=0x01
A)Enableserialreadout(<SERIAL READOUT>=1)
PinSDOUT isNOT inhigh-impedancestate;itisforcedlowbythedevice(<SERIAL READOUT>=0)
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Figure 10. Serial Readout
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T0108-01
t1
t3
t2
PowerSupply
AVDD,DRVDD
RESET
SEN
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RESET TIMING (ONLY WHEN SERIAL INTERFACE IS USED)
Typical values at 25°C, min and max values across the full temperature range TMIN = –40°C to TMAX = 85°C (unless otherwise
noted). PARAMETER CONDITIONS MIN TYP MAX UNIT
t1Power-on delay Delay from power-up of AVDD and DRVDD to RESET pulse active 1 ms
10 ns
t2Reset pulse width Pulse width of active RESET signal 1(1) ms
t3Register write delay Delay from RESET disable to SEN active 100 ns
(1) The reset pulse is needed only when using the serial interface configuration. If the pulse width is greater than 1msec, the device could
enter the parallel configuration mode briefly and then return back to serial interface mode.
NOTE: A high-going pulse on RESET pin is required in serial interface mode in case of initialization through hardware reset.
For parallel interface operation, RESET has to be tied permanently HIGH.
Figure 11. Reset Timing Diagram
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SERIAL REGISTER MAP
Table 8. Summary of Functions Supported by Serial Interface (1)
REGISTER REGISTER FUNCTIONS
ADDRESS
A7–A0 D7 D6 D5 D4 D3 D2 D1 D0
IN HEX
00 <RESET> 0 0 0 0 0 0 <SERIAL
Software Reset READOUT>
20 0 0 0 0 0 <ENABLE 0 0
LOW
SPEED
MODE>
3F 0 <REF> 0 0 0 0 <STANDBY> 0
Internal or external reference
40 0 0 0 0 <POWER DOWN MODES>
41 <LVDS CMOS> 0 0 0 0 0 0 0
Output interface
44 <CLKOUT EDGE CONTROL> 0 0
50 0 <ENABLE INDIVIDUAL 0 0 0 <DATA FORMAT> 0
CHANNEL CONTROL> 2s comp or offset binary
51 <CUSTOM PATTERN LOW>
52 0 0 <CUSTOM PATTERN HIGH>
53 0 <ENABLE OFFSET 0
CORRECTION – CH A>
55 <GAIN PROGRAMMABILITY – CH A> <OFFSET CORRECTION TIME
0 to 6 dB in 0.5 dB steps CONSTANT – CH A>
57 0 <FINE GAIN ADJUST – CH A>
+0.001 dB to +0.134 dB, in 128 steps
62 0 0 0 0 0 <TEST PATTERNS – CH A>
63 0 0 <OFFSET PEDESTAL – CH A>
66 0 <ENABLE OFFSET 0 0 0 0 0 0
CORRECTION – CH B>
68 <GAIN PROGRAMMABILITY – CH B> <OFFSET CORRECTION TIME
0 to 6 dB in 0.5 dB steps CONSTANT – CH B>
6A 0 <FINE GAIN ADJUST – CH B>
+0.001 dB to +0.134 dB, in 128 steps
75 0 0 0 0 0 <TEST PATTERNS – CH B>
76 0 0 <OFFSET PEDESTAL – CH B>
(1) Multiple functions in a register can be programmed in a single write operation.
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DESCRIPTION OF SERIAL REGISTERS
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
00 <RESET> 00000 <SERIAL READOUT>
Software Reset
D7 <RESET>
1 Software reset applied – resets all internal registers and self-clears to 0.
D0 <SERIAL READOUT>
0 Serial readout disabled. SDOUT is forced low by the device (and not put in high impedance state).
1 Serial readout enabled, Pin SDOUT functions as serial data readout.
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
20 00000 <ENABLE LOW SPEED MODE> 0 0
D2 <ENABLE LOW SPEED MODE>
0 LOW SPEED mode disabled. Use for sampling frequency > 80 MSPS
1 Enable LOW SPEED mode for sampling frequencies ≤80 MSPS.
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
3F 0 <REF> 0 0 0 <STANDBY> 0
D6-D5 <REF> Internal or external reference selection
00 Internal reference enabled
01
10
11 External reference enabled
D1 <STANDBY>
0 Normal operation
1 Both ADC channels are put in standby. Internal references, output buffers are active. This results in
quick wake-up time from standby.
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
40 0 0 0 0 POWER DOWN MODES
D3-D0 <POWER DOWN MODES>
0000 Pins CTRL1, CTRL2, and CTRL3 determine power down modes.
1000 Normal operation
1001 Output buffer disabled for channel B
1010 Output buffer disabled for channel A
1011 Output buffer disabled for channel A and B
1100 Global power down
1101 Channel B standby
1110 Channel A standby
1111 Multiplexed mode, MUX- (only with CMOS interface)
Channel A and B data is multiplexed and output on DA13 to DA0 pins. Refer to the Multiplexed
Output Mode section in the APPLICATION INFORMATION for additional information.
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A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
41 <LVDS 0000000
CMOS>
D7 <LVDS CMOS>
0 Parallel CMOS interface
1 DDR LVDS interface
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
44 <CLKOUT EDGE CONTROL> 0 0
Output clock edge control
LVDS interface
D7-D5 <CLKOUT POSN> Output clock rising edge position (2)
000, 100 Default output clock position (refer to timing specification table)
101 Falling edge shifted (delayed) by + (4/26)×Ts(1)
110 Falling edge shifted (advanced) by – (7/26)×Ts
111 Falling edge shifted (advanced) by – (4/26)×Ts
D4-D2 <CLKOUT POSN> Output clock falling edge position (2)
000, 100 Default output clock position (refer to timing specification table)
101 Rising edge shifted (delayed) by + (4/26)×Ts
110 Rising edge shifted (advanced) by – (7/26)×Ts
111 Rising edge shifted (advanced) by – (4/26)×Ts
CMOS interface
D7-D5 <CLKOUT POSN> Output clock rising edge position (2)
000, 100 Default output clock position (refer to timing specification table)
101 Rising edge shifted (delayed) by + (4/26)×Ts
110 Rising edge shifted (advanced) by – (7/26)×Ts
111 Rising edge shifted (advanced) by – (4/26)×Ts
D4-D2 <CLKOUT POSN> Output clock falling edge position (2)
000, 100 Default output clock position (refer to timing specification table)
101 Falling edge shifted (delayed) by + (4/26)×Ts
110 Falling edge shifted (advanced) by – (7/26)×Ts
111 Falling edge shifted (advanced) by – (4/26)×Ts
(1) Ts = 1 / sampling frequency
(2) Keep the same duty cycle, move both edges by the same amount (i.e., write both D<4:2> and D<7:5> to be
the same value).
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Sampling Time Period Ts
D<4:2> = 101
Moves rising edge
by +(4/26)Ts
D<7:5> = 101
Moves falling edge
by +(4/26)Ts
+(4/26)Ts
+(4/26)Ts
T0490-01
D<4:2> = 000
Default position
of rising edge
D<7:5> = 000
Default position
of falling edge
D<4:2> = 110
Moves rising edge
by –(7/26)Ts
–(7/26)Ts –(7/26)Ts
D<7:5> = 110
Moves falling edge
by –(7/26)Ts
–(4/26)Ts –(4/26)Ts
D<4:2> = 111
Moves rising edge
by –(4/26)Ts
D<7:5> = 111
Moves falling edge
by –(4/26)Ts
Data
CLKM
CLKP
CLKM
CLKP
CLKM
CLKP
CLKM
CLKP
D<7:5>=101
Movesrisingedge
by+(4/26)Ts
D<4:2>=000
Defaultposition
offallingedge
D<7:5>=000
Defaultposition
ofrisingedge
Sampling TimePeriod Ts
D<4:2>=101
Movesfallingedge
by+(4/26)Ts
+(4/26)Ts
+(4/26)Ts
T0491-01
D<7:5>=110
Movesrisingedge
by –(7/26)Ts
–(7/26)Ts –(7/26)Ts
D<4:2>=110
Movesfallingedge
by –(7/26)Ts
–(4/26)Ts –(4/26)Ts
D<7:5>=111
Movesrisingedge
by –(4/26)Ts
D<4:2>=111
Movesfallingedge
by –(4/26)Ts
Data
CLKOUT
CLKOUT
CLKOUT
CLKOUT
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NOTES: 1. Keep the same duty cycle, move both edges by same amount (i.e. write both D<4:2> and D<7:5> to be the same
value).
2. Refer to timing specification table for default output clock position.
Figure 12. LVDS Interface Output Clock Edge Movement (Serial Register 0x44)
NOTES: 1. Keep the same duty cycle, move both edges by same amount (i.e. write both D<4:2> and D<7:5> to be the same
value).
2. Refer to timing specification table for default output clock position.
Figure 13. CMOS Interface Output Clock Edge Movement (Serial Register 0x44)
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A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
50 0 <ENABLE INDEPENDENT 0 0 0 <DATA FORMAT> 0
CHANNEL CONTROL> 2s complement or offset binary
D6 <ENABLE INDEPENDENT CHANNEL CONTROL>
0Common control – both channels use common control settings for test patterns, offset correction,
fine gain, gain correction and SNR Boost functions. These settings can be specified in a single set of
registers.
1Independent control – both channels can be programmed with independent control settings for test
patterns, offset correction and SNR Boost functions. Separate registers are available for each
channel.
D2-D1 <DATA FORMAT>
10 2s complement
11 Offset binary
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
51 <Custom Pattern Low>
52 0 0 <Custom Pattern High>
D7-D0 <CUSTOM PATTERN LOW>
8 lower bits of custom pattern available at the output instead of ADC data.
D5-D0 <CUSTOM PATTERN HIGH>
6 upper bits of custom pattern available at the output instead of ADC data
Use this mode along with “Test Patterns” (register 0x62).
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
53 0 <ENABLE OFFSET CORRECTION – Common/Ch A> Offset 0 0 0 0 0 0
correction enable
D6 <ENABLE OFFSET CORRECTION – Common/Ch A>
Offset correction enable control for both channels (with common control) or for channel A only (with
independent control).
0 Offset correction disabled
1 Offset correction enabled
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ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
55 <GAIN – Common/Ch A> <OFFSET CORR TIME CONSTANT – Common/Ch A>
Offset correction time constant
D7-D4 <GAIN – Common/Ch A>
Gain control for both channels (with common control) or for channel A only (with independent
control).
0000 0 dB gain, default after reset
0001 0.5 dB gain
0010 1.0 dB gain
0011 1.5 dB gain
0100 2.0 dB gain
0101 2.5 dB gain
0110 3.0 dB gain
0111 3.5 dB gain
1000 4.0 dB gain
1001 4.5 dB gain
1010 5.0 dB gain
1011 5.5 dB gain
1100 6.0 dB gain
D3-D0 <OFFSET CORR TIME CONSTANT – Common/Ch A>
Correction loop time constant in number of clock cycles.
Applies to both channels (with common control) or for channel A only (with independent control).
0000 256 k
0001 512 k
0010 1 M
0011 2 M
0100 4 M
0101 8 M
0110 16 M
0111 32 M
1000 64 M
1001 128 M
1010 256 M
1011 512 M
26 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
57 0 <FINE GAIN ADJUST – Common/Ch A>
+0.001 dB to +0.134 dB, in 128 steps
Using the FINE GAIN ADJUST register bits, the channel gain can be trimmed in fine steps. The trim is only
additive, has 128 steps and a range of 0.134dB. The relation between the FINE GAIN ADJUST bits and the
trimmed channel gain is:
ΔChannel gain = 20*log10[1 + (FINE GAIN ADJUST/8192)]
Note that the total device gain = ADC gain + ΔChannel gain. The ADC gain is determined by register bits
<GAIN PROGRAMMABILITY>
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
62 0 0 0 0 0 <TEST PATTERNS>
D2-D0 <TEST PATTERNS> Test Patterns to verify data capture.
Applies to both channels (with common control) or for channel A only (with independent control).
000 Normal operation
001 Outputs all zeros
010 Outputs all ones
011 Outputs toggle pattern – see Figure 14 and Figure 15 for test pattern timing diagrams for LVDS and
CMOS modes.
In ADS62P49/48, output data <D13:D0> alternates between 01010101010101 and 10101010101010
every clock cycle.
In ADS62P29/28, output data <D11:D0> alternates between 010101010101 and 101010101010 every
clock cycle.
100 Outputs digital ramp
In ADS62P49/48, output data increments by one LSB (14-bit) every clock cycle from code 0 to code
16383
In ADS62P29/28, output data increments by one LSB (12-bit) every 4th clock cycle from code 0 to
code 4095
101 Outputs custom pattern (use registers 0x51, 0x52 for setting the custom pattern), see Figure 16 for an
example of a custom pattern.
110 Unused
111 Unused
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 27
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
DA0,DB0
DA2,DB2
DA10,DB10
•
•
•
•
•
•
DA12,DB12
0
(D0) 0
0
(D2) 0
0
(D10) 0
0
(D12) 0
1 1
1 1
1 1
1 1
1
(D1) 1
1
(D3) 1
1
(D11) 1
1
(D13) 1
0 0
0 0
0 0
0 0
CLKOUTM
CLKOUTP
SampleN+1 SampleN+3SampleN SampleN+2
T0485-01
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
NOTES: 1. Even bits output at the rising edge of CLKOUTP, and odd bits output at falling edge of CLKOUTP.
2. Output toggles at half the sampling rate (Fs/2) in this test mode.
Figure 14. Output Toggle Pattern (Serial Register 0x62, D<2:0> = 011) in LVDS Mode
28 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
DA0,DB0
DA1,DB1
DA12,DB12
•
•
•
•
•
•
DA13,DB13
0 0
00
0 0
00
11
1
1 1
1
1 1
CLKOUT
SampleN+1 SampleN+3SampleN SampleN+2
T0486-01
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
NOTE: Output toggles at half the sampling rate (Fs/2) in this test mode.
Figure 15. Output Toggle Pattern (Serial Register 0x62, D<2:0> = 011) in CMOS Mode
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 29
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
DA0,DB0
DA2,DB2
DA10,DB10
•
•
•
•
•
•
DA12,DB12
0
(D0) 00 0
0
(D2) 00 0
0
(D10) 00 0
0
(D12) 00 0
1
(D1) 11 1
1
(D3) 11 1
1
(D11) 11 1
1
(D13) 11 1
CLKOUTM
CLKOUTP
SampleN+1 SampleN+3SampleN SampleN+2
T0485-02
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
Example: Register 0x51 = 0xAA and Register 0x52 = 0x2A to toggle output at Fs
NOTES: 1. Even bits output at the rising edge of CLKOUTP, and odd bits output at falling edge of CLKOUTP.
2. Output toggles at the sampling rate (Fs) in this test mode.
Figure 16. Output Custom Pattern (Serial Register 0x62, D<2:0> = 101) in LVDS Mode
30 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
63 0 0 <OFFSET PEDESTAL – Common/Ch A>
D5-D0 <OFFSET PEDESTAL – Common/Ch A>
When the offset correction is enabled, the final converged value (after the offset is corrected) will
be the ideal ADC mid-code value (=8192 for P49/48, = 2048 for P29/28). A pedestal can be
added to the final converged value by programming these bits. So, the final converged value will
be = ideal mid-code + PEDESTAL.
See "Offset Correction" in application section.
Applies to both channels (with common control) or for channel A only (with independent control).
011111 PEDESTAL = 31 LSB
011110 PEDESTAL = 30 LSB
011101 PEDESTAL = 29 LSB
….
000000 PEDESTAL = 0
….
111111 PEDESTAL = –1 LSB
111110 PEDESTAL = –2 LSB
….
100000 PEDESTAL = –32 LSB
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
66 0 <ENABLE OFFSET CORRECTION – CH B> Offset 0 0 0 0 0 0
correction enable
D6 <ENABLE OFFSET CORRECTION – CH B>
Offset correction enable control for channel B (only with independent control).
0 offset correction disabled
1 offset correction enabled
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 31
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
68 <GAIN – CH B> <OFFSET CORR TIME CONSTANT – CH B>
Offset correction time constant
D7-D4 <GAIN – CH B> Gain programmability to 0.5 dB steps.
Applies to channel B (only with independent control).
0000 0 dB gain, default after reset
0001 0.5 dB gain
0010 1.0 dB gain
0011 1.5 dB gain
0100 2.0 dB gain
0101 2.5 dB gain
0110 3.0 dB gain
0111 3.5 dB gain
1000 4.0 dB gain
1001 4.5 dB gain
1010 5.0 dB gain
1011 5.5 dB gain
1100 6.0 dB gain
D3-D0 OFFSET CORR TIME CONSTANT – CH B> Time constant of correction loop in number of clock
cycles.
Applies to channel B (only with independent control)
0000 256 k
0001 512 k
0010 1 M
0011 2 M
0100 4 M
0101 8 M
0110 16 M
0111 32 M
1000 64 M
1001 128 M
1010 256 M
1011 512 M
32 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
6A <FINE GAIN ADJUST – CH B>
+0.001 dB to +0.134 dB, in 128 steps
Using the FINE GAIN ADJUST register bits, the channel gain can be trimmed in fine steps. The trim is only
additive, has 128 steps and a range of 0.134dB. The relation between the FINE GAIN ADJUST bits and the
trimmed channel gain is:
ΔChannel gain = 20*log10[1 + (FINE GAIN ADJUST/8192)]
Note that the total device gain = ADC gain + ΔChannel gain. The ADC gain is determined by register bits
<GAIN PROGRAMMABILITY>
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
75 0 0 0 <TEST PATTERNS – CH B>
D2-D0 <TEST PATTERNS> Test Patterns to verify data capture.
Applies to channel B (only with independent control)
000 Normal operation
001 Outputs all zeros
010 Outputs all ones
011 Outputs toggle pattern – see Figure 14 and Figure 15 for LVDS and CMOS modes.
In ADS62P49/48, output data <D13:D0> alternates between 01010101010101 and
10101010101010 every clock cycle.
In ADS62P29/28, output data <D11:D0> alternates between 010101010101 and 101010101010
every clock cycle.
100 Outputs digital ramp
In ADS62P49/48, output data increments by one LSB (14-bit) every clock cycle from code 0 to
code 16383
In ADS62P29/28, output data increments by one LSB (12-bit) every 4th clock cycle from code 0 to
code 4095
101 Outputs custom pattern (use registers 0x51, 0x52 for setting the custom pattern), see Figure 16 for
an example of a custom pattern.
110 Unused
111 Unused
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 33
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
A7–A0 IN HEX D7 D6 D5 D4 D3 D2 D1 D0
76 0 0 <OFFSET PEDESTAL – Common/CH B>
D5-D0 <OFFSET PEDESTAL – Common/CH B>
When the offset correction is enabled, the final converged value (after the offset is corrected) will
be the ideal ADC mid-code value (=8192 for P49/48, = 2048 for P29/28). A pedestal can be
added to the final converged value by programming these bits. So, the final converged value will
be = ideal mid-code + PEDESTAL. See "Offset Correction" in application section.
Applies to channel B (only with independent control).
011111 PEDESTAL = 31 LSB
011110 PEDESTAL = 30 LSB
011101 PEDESTAL = 29 LSB
….
000000 PEDESTAL = 0
….
111111 PEDESTAL = –1 LSB
111110 PEDESTAL = –2 LSB
….
100000 PEDESTAL = –32 LSB
34 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ThermalPad
(ConnectedtoDRGND)
48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33
RGCPackage
(TopView)
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
64
18
63
19
62
20
61
21
60
22
59
23
58
24
57
25
56
26
55
27
54
28
53
29
52
30
51
31
50
32
49
P0056-14
AGND
AGND
INP_B
NC
CM
INM_A
AGND
AGND
CLKP
CLKM
CLKOUTP
CLKOUTM
DRVDD DRVDD
CTRL3
DB0M
DB0P
SDOUT
DRGND
DB4M
DB4P
DB6P
DB6M
DB8P
DB8M
DB10M
DA10M
DA8M
DA8P
DA4P
DA2P
DA4M
DA0P
DA2M
DA0M
AVDD
SDATA
SCLK
CTRL1
CTRL2
AGND
RESET
AVDD
INM_B
AGND
INP_A
SEN
AVDD
AGND
AGND
DRGND
DRVDD
DRGND
DRVDD
DB10P
DA10P
DB2M
DB2P
DB12M
DB12P
DA6P
DA6M
DA12M
DA12P
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
DEVICE INFORMATION
PIN CONFIGURATION (LVDS MODE) – ADS62P49/P48
Figure 17.
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 35
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ThermalPad
(ConnectedtoDRGND)
48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33
RGCPackage
(TopView)
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
64
18
63
19
62
20
61
21
60
22
59
23
58
24
57
25
56
26
55
27
54
28
53
29
52
30
51
31
50
32
49
P0056-15
AGND
AGND
INP_B
NC
CM
INM_A
AGND
AGND
CLKP
CLKM
CLKOUTP
CLKOUTM
DRVDD DRVDD
CTRL3
NC
NC
SDOUT
DRGND
DB2M
DB2P
DB4P
DB4M
DB6P
DB6M
DB8M
DA8M
DA6M
DA6P
DA2P
DA0P
DA2M
NC
DA0M
NC
AVDD
SDATA
SCLK
CTRL1
CTRL2
AGND
RESET
AVDD
INM_B
AGND
INP_A
SEN
AVDD
AGND
AGND
DRGND
DRVDD
DRGND
DRVDD
DB8P
DA8P
DB0M
DB0P
DB10M
DB10P
DA4P
DA4M
DA10M
DA10P
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
PIN CONFIGURATION (LVDS MODE) – ADS62P29/P28
Figure 18.
PIN ASSIGNMENTS (LVDS MODE) – ADS62P49/P48 and ADS62P29/P28
PIN NO. OF I/O DESCRIPTION
PINS
NAME NO.
AVDD 16, 33, 34 3 I Analog power supply
17, 18, 21, 24,
AGND 8 I Analog ground
27, 28, 31, 32
CLKP, CLKM 25, 26 2 I Differential clock input
INP_A, INM_A 29, 30 2 I Differential analog input, Channel A
INP_B, INM_B 19, 20 2 I Differential analog input, Channel B
VCM 23 1 IO Internal reference mode – Common-mode voltage output.
External reference mode – Reference input. The voltage forced on this pin sets the
internal references.
RESET 12 1 I Serial interface RESET input.
When using the serial interface mode, the user must initialize internal registers through
hardware RESET by applying a high-going pulse on this pin or by using software reset
option. Refer to Serial Interface section.
36 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
PIN ASSIGNMENTS (LVDS MODE) – ADS62P49/P48 and ADS62P29/P28 (continued)
PIN NO. OF I/O DESCRIPTION
PINS
NAME NO.
In parallel interface mode, the user has to tie RESET pin permanently high. (SCLK and
SEN are used as parallel control pins in this mode)
The pin has an internal 100 kΩpull-down resistor.
SCLK 13 1 I This pin functions as serial interface clock input when RESET is low.
It controls selection of internal or external reference when RESET is tied high. See
Table 5 for detailed information.
The pin has an internal 100 kΩpull-down resistor.
SDATA 14 1 I Serial interface data input.
The pin has an internal 100KΩpull-down resistor.
It has no function in parallel interface mode and can be tied to ground.
SEN 15 1 I This pin functions as serial interface enable input when RESET is low.
It controls selection of data format and interface type when RESET is tied high. See
Table 6 for detailed information.
The pin has an internal 100 kΩpull-up resistor to AVDD
This pin functions as serial interface register readout, when the <SERIAL READOUT> bit
SDOUT 64 1 O is enabled.
When <SERIAL READOUT> = 0, this pin forces logic LOW and is not 3-stated.
CTRL1 35 1 I Digital control input pins. Together, they control various power down modes.
CTRL2 36 1 I The pin has an internal 100kΩpull-down resistor.
CTRL3 37 1 I
CLKOUTP 57 1 O Differential output clock, true
CLKOUTM 56 1 O Differential output clock, complement
DA0P, DA0M 2 O Differential output data pair, D0 and D1 multiplexed – Channel A
DA2P, DA2M 2 O Differential output data D2 and D3 multiplexed – Channel A
DA4P, DA4M 2 O Differential output data D4 and D5 multiplexed – Channel A
DA6P, DA6M 2 O Differential output data D6 and D7 multiplexed – Channel A
DA8P, DA8M 2 O Differential output data D8 and D9 multiplexed – Channel A
DA10P, 2 O Differential output data D10 and D11 multiplexed – Channel A
DA10M
DA12P, 2 O Differential output data D12 and D13 multiplexed – Channel A
Refer to
DA12M Figure 17 and
DB0P, DB0M 2 O Differential output data pair, D0 and D1 multiplexed – Channel B
Figure 18
DB2P, DB2M 2 O Differential output data D2 and D3 multiplexed – Channel B
DB4P, DB4M 2 O Differential output data D4 and D5 multiplexed – Channel B
DB6P, DB6M 2 O Differential output data D6 and D7 multiplexed – Channel B
DB8P, DB8M 2 O Differential output data D8 and D9 multiplexed – Channel B
DB10P, 2 O Differential output data D10 and D11 multiplexed – Channel B
DB10M
DB12P, 2 O Differential output data D12 and D13 multiplexed – Channel B
DB12M
DRVDD 1, 38, 48, 58 4 I Output buffer supply
39, 49, 59,
DRGND 4 I Output buffer ground
PAD
Refer to
NC Figure 17 and Do not connect
Figure 18
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 37
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ThermalPad
(ConnectedtoDRGND)
48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33
RGCPackage
(TopView)
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
64
18
63
19
62
20
61
21
60
22
59
23
58
24
57
25
56
26
55
27
54
28
53
29
52
30
51
31
50
32
49
P0056-16
AGND
AGND
INP_B
NC
CM
INM_A
AGND
AGND
CLKP
CLKM
CLKOUT
NC
DRVDD DRVDD
CTRL3
DB0
DB1
SDOUT
DRGND
DB4
DB5
DB7
DB6
DB9
DB8
DB10
DA10
DA8
DA9
DA5
DA3
DA4
DA1
DA2
DA0
AVDD
SDATA
SCLK
CTRL1
CTRL2
AGND
RESET
AVDD
INM_B
AGND
INP_A
SEN
AVDD
AGND
AGND
DRGND
DRVDD
DRGND
DRVDD
DB11
DA11
DB2
DB3
DB12
DB13
DA7
DA6
DA12
DA13
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
PIN CONFIGURATION (CMOS MODE) – ADS62P49/P48
Figure 19.
38 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ThermalPad
(ConnectedtoDRGND)
48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33
RGCPackage
(TopView)
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
64
18
63
19
62
20
61
21
60
22
59
23
58
24
57
25
56
26
55
27
54
28
53
29
52
30
51
31
50
32
49
P0056-17
AGND
AGND
INP_B
NC
CM
INM_A
AGND
AGND
CLKP
CLKM
CLKOUT
NC
DRVDD DRVDD
CTRL3
NC
NC
SDOUT
DRGND
DB2
DB3
DB5
DB4
DB7
DB6
DB8
DA8
DA6
DA7
DA3
DA1
DA2
NC
DA0
NC
AVDD
SDATA
SCLK
CTRL1
CTRL2
AGND
RESET
AVDD
INM_B
AGND
INP_A
SEN
AVDD
AGND
AGND
DRGND
DRVDD
DRGND
DRVDD
DB9
DA9
DB0
DB1
DB10
DB11
DA5
DA4
DA10
DA11
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
PIN CONFIGURATION (CMOS MODE) – ADS62P29/P28
Figure 20.
PIN ASSIGNMENTS (CMOS MODE) – ADS62P49/P48 and ADS62P29/P28
PIN NO. OF I/O DESCRIPTION
PINS
NAME NO.
AVDD 16, 33, 34 3 I Analog power supply
17, 18, 21, 24,
AGND 8 I Analog ground
27, 28, 31, 32
CLKP, CLKM 25, 26 2 I Differential clock input
INP_A, INM_A 29, 30 2 I Differential analog input, Channel A
INP_B, INM_B 19, 20 2 I Differential analog input, Channel B
VCM 23 1 IO Internal reference mode – Common-mode voltage output.
External reference mode – Reference input. The voltage forced on this pin sets the
internal references.
RESET 12 1 I Serial interface RESET input.
When using the serial interface mode, the user MUST initialize internal registers through
hardware RESET by applying a high-going pulse on this pin or by using software reset
option. Refer to SERIAL INTERFACE section.
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 39
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
PIN ASSIGNMENTS (CMOS MODE) – ADS62P49/P48 and ADS62P29/P28 (continued)
PIN NO. OF I/O DESCRIPTION
PINS
NAME NO.
In parallel interface mode, the user has to tie RESET pin permanently high. (SCLK and
SEN are used as parallel control pins in this mode. )
The pin has an internal 100 kΩpull-down resistor.
SCLK 13 1 I This pin functions as serial interface clock input when RESET is low.
It controls selection of internal or external reference when RESET is tied high. See
Table 5 for detailed information.
The pin has an internal 100-kΩpull-down resistor.
SDATA 14 1 I Serial interface data input.
The pin has an internal 100-kΩpull-down resistor.
It has no function in parallel interface mode and can be tied to ground.
SEN 15 1 I This pin functions as serial interface enable input when RESET is low.
It controls selection of data format and interface type when RESET is tied high. See
Table 6 for detailed information.
The pin has an internal 100 kΩpull-up resistor to AVDD.
This pin functions as serial interface register readout, when the <SERIAL READOUT> bit
SDOUT 64 1 O is enabled.
When <SERIAL READOUT> = 0, this pin forces logic LOW and is not 3-stated.
CTRL1 35 1 I Digital control input pins. Together, they control various power down modes.
CTRL2 36 1 I The pin has an internal 100 kΩpull-down resistor.
CTRL3 37 1 I
CLKOUT 57 1 O CMOS output clock
DA0-DA13 Refer to 14 O Channel A ADC output data bits, CMOS levels
Figure 19 and
DB0-DB13 14 O Channel B ADC output data bits, CMOS levels
Figure 20
DRVDD 1, 38, 48, 58 4 I Output buffer supply
39, 49, 59,
DRGND 4 I Output buffer ground
PAD
Refer to
NC Figure 19 and Do not connect
Figure 20
40 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G001
SFDR = 89.5 dBc
SINAD = 73.1 dBFS
SNR = 73.2 dBFS
THD = 88.1 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G002
SFDR = 75 dBc
SINAD = 69.5 dBFS
SNR = 70.7 dBFS
THD = 74.5 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G003
SFDR = 76.5 dBc
SINAD = 67.6 dBFS
SNR = 68.6 dBFS
THD = 73.6 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G004
fIN1 = 185 MHz, –7 dBFS
fIN2 = 190 MHz, –7 dBFS
2-Tone IMD = –85 dBFS
SFDR = 90.2 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G005
fIN1 = 185 MHz, –36 dBFS
fIN2 = 190 MHz, –36 dBFS
2-Tone IMD = –100 dBFS
SFDR = 96.6 dBc
fIN − Input Frequency − MHz
64
68
72
76
80
84
88
92
0 50 100 150 200 250 300 350 400 450 500
SFDR − dBc
G006
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
TYPICAL CHARACTERISTICS – ADS62P49
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
FFT FOR 20 MHz INPUT SIGNAL FFT FOR 170 MHz INPUT SIGNAL
Figure 21. Figure 22.
FFT FOR 300 MHz INPUT SIGNAL FFT FOR 2-TONE INPUT SIGNAL
Figure 23. Figure 24.
FFT FOR 2-TONE INPUT SIGNAL SFDR vs INPUT FREQUENCY
Figure 25. Figure 26.
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 41
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
fIN − Input Frequency − MHz
64
65
66
67
68
69
70
71
72
73
74
0 50 100 150 200 250 300 350 400 450 500
SNR − dBFS
G007
fIN − Input Frequency − MHz
72
74
76
78
80
82
84
86
88
90
92
0 50 100 150 200 250 300 350 400 450 500
SFDR − dBc
G008
Input adjusted to get −1dBFS input
1 dB
0 dB
6 dB
2 dB
3 dB
4 dB
5 dB
fIN − Input Frequency − MHz
62
63
64
65
66
67
68
69
70
71
72
0 50 100 150 200 250 300 350 400 450 500
SINAD − dBFS
G009
2 dB
5 dB
1 dB
0 dB
3 dB
4 dB
6 dB
69
71
73
75
77
79
81
Input Amplitude − dBFS
SFDR − dBc, dBFS
G010
SNR − dBFS
SFDR (dBc)
SFDR (dBFS)
SNR (dBFS)
0
20
40
60
80
100
120
−100 −90 −80 −70 −60 −50 −40 −30 −20 −10 0
fIN = 60 MHz
TA − Free-Air Temperature − °C
78
79
80
81
82
83
84
85
86
87
88
−40 −20 0 20 40 60 80
SFDR − dBc
G012
DRVDD = 1.8 V
fIN = 60 MHz
AVDD = 3.6 V AVDD = 3.5 V AVDD = 3.4 V
AVDD = 3.15 VAVDD = 3.2 V
AVDD = 3.3 V
SNR − dBFS
70
72
74
76
78
80
VIC − Common-Mode Input Voltage − V
SFDR − dBc
G011
78
80
82
84
86
88
1.35 1.40 1.45 1.50 1.55 1.60 1.65 1.70
fIN = 60 MHz
SNR
SFDR
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
TYPICAL CHARACTERISTICS – ADS62P49 (continued)
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR vs INPUT FREQUENCY SFDR vs INPUT FREQUENCY ACROSS GAIN
Figure 27. Figure 28.
SINAD vs INPUT FREQUENCY ACROSS GAIN PERFORMANCE vs INPUT AMPLITUDE, SINGLE TONE
Figure 29. Figure 30.
PERFORMANCE vs COMMON-MODE INPUT VOLTAGE SFDR vs AVDD SUPPLY VOLTAGE
Figure 31. Figure 32.
42 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
TA − Free-Air Temperature − °C
71.00
71.25
71.50
71.75
72.00
72.25
72.50
−40 −20 0 20 40 60 80
SNR − dBFS
G013
DRVDD = 1.8 V
fIN = 60 MHz
AVDD = 3.6 V
AVDD = 3.5 V
AVDD = 3.2 V
AVDD = 3.3 V
AVDD = 3.4 V
AVDD = 3.15 V
SNR − dBFS
70
71
72
73
74
75
76
77
78
DRVDD − Supply Voltage − V
SFDR − dBc
G014
SNR
SFDR
AVDD = 3.3 V
fIN = 60 MHz
78
79
80
81
82
83
84
85
86
1.70 1.74 1.78 1.82 1.86 1.90
SNR − dBFS
70
71
72
73
74
75
76
77
78
SFDR − dBc
Input Clock Amplitude − VPP G015
74
76
78
80
82
84
86
88
90
0.0 0.5 1.0 1.5 2.0 2.5
SNR
SFDR
fIN = 60 MHz
SNR − dBFS
70
71
72
73
74
75
76
77
78
Input Clock Duty Cycle − %
SFDR − dBc
G016
SNR
SFDR
fIN = 20 MHz
76
78
80
82
84
86
88
90
92
30 35 40 45 50 55 60 65
SNR − dBFS
70
72
74
76
78
80
VVCM − VCM Voltage − V
SFDR − dBc
G017
76
78
80
82
84
86
1.30 1.35 1.40 1.45 1.50 1.55 1.60 1.65 1.70
fIN = 60 MHz
External Reference Mode
SNR
SFDR
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
TYPICAL CHARACTERISTICS – ADS62P49 (continued)
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR vs AVDD SUPPLY VOLTAGE PERFORMANCE vs DRVDD SUPPLY VOLTAGE
Figure 33. Figure 34.
PERFORMANCE vs INPUT CLOCK AMPLITUDE PERFORMANCE vs INPUT CLOCK DUTY CYCLE
Figure 35. Figure 36.
PERFORMANCE IN EXTERNAL REFERENCE MODE
Figure 37.
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 43
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G018
SFDR = 84.1 dBc
SINAD = 73.1 dBFS
SNR = 73.4 dBFS
THD = 83.5 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G019
SFDR = 77.4 dBc
SINAD = 70.1 dBFS
SNR = 70.9 dBFS
THD = 77 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G020
SFDR = 70.1 dBc
SINAD = 66 dBFS
SNR = 68.8 dBFS
THD = 68.2 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G021
fIN1 = 185 MHz, –7 dBFS
fIN2 = 190 MHz, –7 dBFS
2-Tone IMD = –84.7 dBFS
SFDR = –97.2 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G022
fIN1 = 185 MHz, –36 dBFS
fIN2 = 190 MHz, –36 dBFS
2-Tone IMD = –107.1 dBFS
SFDR = –98.8 dBc
fIN − Input Frequency − MHz
68
72
76
80
84
88
92
0 50 100 150 200 250 300 350 400 450 500
SFDR − dBc
G023
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
TYPICAL CHARACTERISTICS – ADS62P48
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
FFT FOR 20 MHz INPUT SIGNAL FFT FOR 170 MHz INPUT SIGNAL
Figure 38. Figure 39.
FFT FOR 300 MHz INPUT SIGNAL FFT FOR 2-TONE INPUT SIGNAL
Figure 40. Figure 41.
FFT FOR 2-TONE INPUT SIGNAL SFDR vs INPUT FREQUENCY
Figure 42. Figure 43.
44 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
fIN − Input Frequency − MHz
64
65
66
67
68
69
70
71
72
73
74
0 50 100 150 200 250 300 350 400 450 500
SNR − dBFS
G024
fIN − Input Frequency − MHz
68
72
76
80
84
88
92
96
0 50 100 150 200 250 300 350 400 450 500
SFDR − dBc
G025
Input adjusted to get −1dBFS input
5 dB
6 dB
4 dB
1 dB
0 dB 3 dB
2 dB
fIN − Input Frequency − MHz
62
64
66
68
70
72
74
76
0 50 100 150 200 250 300 350 400 450 500
SINAD − dBFS
G026
0 dB
1 dB 2 dB
3 dB 4 dB 6 dB
5 dB
Input adjusted to get −1dBFS input
69
71
73
75
77
79
81
Input Amplitude − dBFS
SFDR − dBc, dBFS
G027
SNR − dBFS
SFDR (dBc)
SFDR (dBFS)
SNR (dBFS)
0
20
40
60
80
100
120
−100 −90 −80 −70 −60 −50 −40 −30 −20 −10 0
fIN = 60 MHz
TA − Free-Air Temperature − °C
80
81
82
83
84
85
86
87
88
89
90
−40 −20 0 20 40 60 80
SFDR − dBc
G029
DRVDD = 1.8 V
fIN = 20 MHz
AVDD = 3.15 V
AVDD = 3.3 V
AVDD = 3.6 V
SNR − dBFS
70
72
74
76
78
80
VIC − Common-Mode Input Voltage − V
SFDR − dBc
G028
78
80
82
84
86
88
1.35 1.40 1.45 1.50 1.55 1.60 1.65 1.70
fIN = 60 MHz
SNR
SFDR
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
TYPICAL CHARACTERISTICS – ADS62P48 (continued)
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR vs INPUT FREQUENCY SFDR vs INPUT FREQUENCY ACROSS GAIN
Figure 44. Figure 45.
SINAD vs INPUT FREQUENCY ACROSS GAIN PERFORMANCE vs INPUT AMPLITUDE, SINGLE TONE
Figure 46. Figure 47.
PERFORMANCE vs COMMON-MODE INPUT VOLTAGE SFDR vs AVDD SUPPLY VOLTAGE
Figure 48. Figure 49.
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 45
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
TA − Free-Air Temperature − °C
72.50
72.75
73.00
73.25
73.50
73.75
74.00
−40 −20 0 20 40 60 80
SNR − dBFS
G030
AVDD = 3.6 V
AVDD = 3.3 V
AVDD = 3.15 V
DRVDD = 1.8 V
fIN = 20 MHz
SNR − dBFS
70
71
72
73
74
75
76
77
78
DRVDD − Supply Voltage − V
SFDR − dBc
G031
SNR
SFDR
AVDD = 3.3 V
fIN = 20 MHz
78
79
80
81
82
83
84
85
86
1.70 1.74 1.78 1.82 1.86 1.90
SNR − dBFS
70
71
72
73
74
75
76
77
78
SFDR − dBc
Input Clock Amplitude − VPP G032
74
76
78
80
82
84
86
88
90
0.0 0.5 1.0 1.5 2.0 2.5
SNR
SFDR
fIN = 60 MHz
SNR − dBFS
70
71
72
73
74
75
76
77
78
Input Clock Duty Cycle − %
SFDR − dBc
G033
SNR
SFDR
fIN = 20 MHz
78
80
82
84
86
88
90
92
94
30 35 40 45 50 55 60 65
SNR − dBFS
70
72
74
76
78
80
VVCM − VCM Voltage − V
SFDR − dBc
G034
80
82
84
86
88
90
1.30 1.35 1.40 1.45 1.50 1.55 1.60 1.65 1.70
fIN = 60 MHz
External Reference Mode
SNR
SFDR
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
TYPICAL CHARACTERISTICS – ADS62P48 (continued)
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR vs AVDD SUPPLY VOLTAGE PERFORMANCE vs DRVDD SUPPLY VOLTAGE
Figure 50. Figure 51.
PERFORMANCE vs INPUT CLOCK AMPLITUDE PERFORMANCE vs INPUT CLOCK DUTY CYCLE
Figure 52. Figure 53.
PERFORMANCE IN EXTERNAL REFERENCE MODE
Figure 54.
46 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G035
SFDR = 87.8 dBc
SINAD = 70.8 dBFS
SNR = 70.9 dBFS
THD = 84.9 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G036
SFDR = 74.8 dBc
SINAD = 68.4 dBFS
SNR = 69.3 dBFS
THD = 74.6 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G037
SFDR = 76.4 dBc
SINAD = 66.7 dBFS
SNR = 67.5 dBFS
THD = 73.5 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G038
fIN1 = 185 MHz, –7 dBFS
fIN2 = 190 MHz, –7 dBFS
2-Tone IMD = –85.3 dBFS
SFDR = –90.4 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 25 50 75 100 125
Amplitude − dB
G039
fIN1 = 185 MHz, –36 dBFS
fIN2 = 190 MHz, –36 dBFS
2-Tone IMD = –102.9 dBFS
SFDR = –96.3 dBc
fIN − Input Frequency − MHz
68
72
76
80
84
88
92
0 50 100 150 200 250 300 350 400 450 500
SFDR − dBc
G040
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
TYPICAL CHARACTERISTICS – ADS62P29
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
FFT FOR 20 MHz INPUT SIGNAL FFT FOR 170 MHz INPUT SIGNAL
Figure 55. Figure 56.
FFT FOR 300 MHz INPUT SIGNAL FFT FOR 2-TONE INPUT SIGNAL
Figure 57. Figure 58.
FFT FOR 2-TONE INPUT SIGNAL SFDR vs INPUT FREQUENCY
Figure 59. Figure 60.
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 47
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
fIN − Input Frequency − MHz
62
63
64
65
66
67
68
69
70
71
72
0 50 100 150 200 250 300 350 400 450 500
SNR − dBFS
G041
fIN − Input Frequency − MHz
72
74
76
78
80
82
84
86
88
90
92
0 50 100 150 200 250 300 350 400 450 500
SFDR − dBc
G042
Input adjusted to get −1dBFS input
0 dB
1 dB
3 dB
4 dB
6 dB
2 dB
5 dB
fIN − Input Frequency − MHz
62
63
64
65
66
67
68
69
70
71
72
0 50 100 150 200 250 300 350 400 450 500
SINAD − dBFS
G043
2 dB
5 dB
1 dB
0 dB
3 dB
4 dB
6 dB
Input adjusted to get −1dBFS input
55
60
65
70
75
80
85
Input Amplitude − dBFS
SFDR − dBc, dBFS
G044
SNR − dBFS
SFDR (dBc)
SFDR (dBFS)
SNR (dBFS)
0
20
40
60
80
100
120
−70 −60 −50 −40 −30 −20 −10 0
fIN = 60 MHz
TA − Free-Air Temperature − °C
78
79
80
81
82
83
84
85
86
87
88
−40 −20 0 20 40 60 80
SFDR − dBc
G046
DRVDD = 1.8 V
fIN = 60 MHz
AVDD = 3.6 V AVDD = 3.5 V AVDD = 3.4 V
AVDD = 3.15 VAVDD = 3.2 V
AVDD = 3.3 V
SNR − dBFS
68
70
72
74
76
78
VIC − Common-Mode Input Voltage − V
SFDR − dBc
G045
78
80
82
84
86
88
1.35 1.40 1.45 1.50 1.55 1.60 1.65 1.70
fIN = 60 MHz
SNR
SFDR
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
TYPICAL CHARACTERISTICS – ADS62P29 (continued)
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR vs INPUT FREQUENCY SFDR vs INPUT FREQUENCY ACROSS GAIN
Figure 61. Figure 62.
SINAD vs INPUT FREQUENCY ACROSS GAIN PERFORMANCE vs INPUT AMPLITUDE, SINGLE TONE
Figure 63. Figure 64.
PERFORMANCE vs COMMON-MODE INPUT VOLTAGE SFDR vs AVDD SUPPLY VOLTAGE
Figure 65. Figure 66.
48 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
TA − Free-Air Temperature − °C
69.00
69.25
69.50
69.75
70.00
70.25
70.50
−40 −20 0 20 40 60 80
SNR − dBFS
G047
DRVDD = 1.8 V
fIN = 60 MHz
AVDD = 3.5 V
AVDD = 3.2 V
AVDD = 3.15 V AVDD = 3.3 V
AVDD = 3.4 V
AVDD = 3.6 V
SNR − dBFS
68
69
70
71
72
73
74
75
76
DRVDD − Supply Voltage − V
SFDR − dBc
G048
SNR
SFDR
AVDD = 3.3 V
fIN = 60 MHz
78
79
80
81
82
83
84
85
86
1.70 1.74 1.78 1.82 1.86 1.90
SNR − dBFS
68
69
70
71
72
73
74
75
76
SFDR − dBc
Input Clock Amplitude − VPP G049
74
76
78
80
82
84
86
88
90
0.0 0.5 1.0 1.5 2.0 2.5
SNR
SFDR
fIN = 60 MHz
SNR − dBFS
68
69
70
71
72
73
74
75
76
Input Clock Duty Cycle − %
SFDR − dBc
G050
SNR
SFDR
fIN = 20 MHz
76
78
80
82
84
86
88
90
92
30 35 40 45 50 55 60 65
SNR − dBFS
68
70
72
74
76
78
VVCM − VCM Voltage − V
SFDR − dBc
G051
76
78
80
82
84
86
1.30 1.35 1.40 1.45 1.50 1.55 1.60 1.65 1.70
fIN = 60 MHz
External Reference Mode
SNR
SFDR
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
TYPICAL CHARACTERISTICS – ADS62P29 (continued)
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR vs AVDD SUPPLY VOLTAGE PERFORMANCE vs DRVDD SUPPLY VOLTAGE
Figure 67. Figure 68.
PERFORMANCE vs INPUT CLOCK AMPLITUDE PERFORMANCE vs INPUT CLOCK DUTY CYCLE
Figure 69. Figure 70.
PERFORMANCE IN EXTERNAL REFERENCE MODE
Figure 71.
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 49
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G052
SFDR = 84 dBc
SINAD = 70.6 dBFS
SNR = 70.8 dBFS
THD = 83.4 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G053
SFDR = 77.6 dBc
SINAD = 68.7 dBFS
SNR = 69.2 dBFS
THD = 77.2 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G054
SFDR = 70.1 dBc
SINAD = 65.4 dBFS
SNR = 67.8 dBFS
THD = 68.2 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G055
fIN1 = 185 MHz, –7 dBFS
fIN2 = 190 MHz, –7 dBFS
2-Tone IMD = –84.8 dBFS
SFDR = 97.5 dBc
f − Frequency − MHz
−140
−120
−100
−80
−60
−40
−20
0
0 20 40 60 80 100
Amplitude − dB
G056
fIN1 = 185 MHz, –36 dBFS
fIN2 = 190 MHz, –36 dBFS
2-Tone IMD = –106.3 dBFS
SFDR = 98.4 dBc
fIN − Input Frequency − MHz
68
72
76
80
84
88
92
0 50 100 150 200 250 300 350 400 450 500
SFDR − dBc
G057
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
TYPICAL CHARACTERISTICS – ADS62P28
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
FFT FOR 20 MHz INPUT SIGNAL FFT FOR 170 MHz INPUT SIGNAL
Figure 72. Figure 73.
FFT FOR 300 MHz INPUT SIGNAL FFT FOR 2-TONE INPUT SIGNAL
Figure 74. Figure 75.
FFT FOR 2-TONE INPUT SIGNAL SFDR vs INPUT FREQUENCY
Figure 76. Figure 77.
50 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
fIN − Input Frequency − MHz
64
65
66
67
68
69
70
71
72
0 50 100 150 200 250 300 350 400 450 500
SNR − dBFS
G058
fIN − Input Frequency − MHz
66
69
72
75
78
81
84
87
90
93
96
0 50 100 150 200 250 300 350 400 450 500
SFDR − dBc
G059
Input adjusted to get −1dBFS input
0 dB 1 dB
2 dB
3 dB
4 dB
5 dB
6 dB
fIN − Input Frequency − MHz
62
63
64
65
66
67
68
69
70
71
72
0 50 100 150 200 250 300 350 400 450 500
SINAD − dBFS
G060
0 dB 1 dB
2 dB
3 dB
4 dB 5 dB 6 dB
Input adjusted to get −1dBFS input
55
60
65
70
75
80
85
Input Amplitude − dBFS
SFDR − dBc, dBFS
G061
SNR − dBFS
SFDR (dBc)
SFDR (dBFS)
SNR (dBFS)
0
20
40
60
80
100
120
−100 −90 −80 −70 −60 −50 −40 −30 −20 −10 0
fIN = 60 MHz
TA − Free-Air Temperature − °C
80
81
82
83
84
85
86
87
88
89
90
−40 −20 0 20 40 60 80
SFDR − dBc
G063
AVDD = 3.3 V
AVDD = 3.15 V
DRVDD = 1.8 V
fIN = 20 MHz
AVDD = 3.6 V
SNR − dBFS
68
70
72
74
76
78
VIC − Common-Mode Input Voltage − V
SFDR − dBc
G062
78
80
82
84
86
88
1.35 1.40 1.45 1.50 1.55 1.60 1.65 1.70
fIN = 60 MHz
SNR
SFDR
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
TYPICAL CHARACTERISTICS – ADS62P28 (continued)
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR vs INPUT FREQUENCY SFDR vs INPUT FREQUENCY ACROSS GAIN
Figure 78. Figure 79.
SINAD vs INPUT FREQUENCY ACROSS GAIN PERFORMANCE vs INPUT AMPLITUDE, SINGLE TONE
Figure 80. Figure 81.
PERFORMANCE vs COMMON-MODE INPUT VOLTAGE SFDR vs AVDD SUPPLY VOLTAGE
Figure 82. Figure 83.
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Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
TA − Free-Air Temperature − °C
70.00
70.25
70.50
70.75
71.00
−40 −20 0 20 40 60 80
SNR − dBFS
G064
AVDD = 3.3 V
AVDD = 3.6 V
AVDD = 3.15 V
DRVDD = 1.8 V
fIN = 20 MHz
SNR − dBFS
70
71
72
73
74
75
76
77
78
DRVDD − Supply Voltage − V
SFDR − dBc
G065
SNR
SFDR
AVDD = 3.3 V
fIN = 20 MHz
78
79
80
81
82
83
84
85
86
1.70 1.74 1.78 1.82 1.86 1.90
SNR − dBFS
68
69
70
71
72
73
74
75
76
SFDR − dBc
Input Clock Amplitude − VPP G066
74
76
78
80
82
84
86
88
90
0.0 0.5 1.0 1.5 2.0 2.5
SNR
SFDR
fIN = 60 MHz
SNR − dBFS
68
69
70
71
72
73
74
75
76
Input Clock Duty Cycle − %
SFDR − dBc
G067
SNR
SFDR
fIN = 20 MHz
80
82
84
86
88
90
92
94
96
30 35 40 45 50 55 60 65
SNR − dBFS
68
70
72
74
76
78
VVCM − VCM Voltage − V
SFDR − dBc
G068
80
82
84
86
88
90
1.30 1.35 1.40 1.45 1.50 1.55 1.60 1.65 1.70
fIN = 60 MHz
External Reference Mode
SNR
SFDR
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
TYPICAL CHARACTERISTICS – ADS62P28 (continued)
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR vs AVDD SUPPLY VOLTAGE PERFORMANCE vs DRVDD SUPPLY VOLTAGE
Figure 84. Figure 85.
PERFORMANCE vs INPUT CLOCK AMPLITUDE PERFORMANCE vs INPUT CLOCK DUTY CYCLE
Figure 86. Figure 87.
PERFORMANCE IN EXTERNAL REFERENCE MODE
Figure 88.
52 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
f − Frequency − MHz
−70
−65
−60
−55
−50
−45
−40
−35
−30
20 70 120 170 220 270
CMRR − dB
G070
−100
−96
−92
−88
−84
−80
−76
0 50 100 150 200 250 300
f − Frequency − MHz
Crosstalk − dB
G069
Signal amplitude on aggressor channel at −0.3 dBFS
fS − Sampling Frequency − MSPS
0.4
0.6
0.8
1.0
1.2
1.4
25 50 75 100 125 150 175 200 225 250
PD − Power Dissipation − W
G072
LVDS
CMOS
fIN = 2.5 MHz
fS − Sampling Frequency − MSPS
0
20
40
60
80
100
120
140
25 50 75 100 125 150 175 200 225 250
DRVDD Current − mA
G073
LVDS
CMOS, No Load
CMOS, 15 pF Load
fIN = 2.5 MHz
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
TYPICAL CHARACTERISTICS – COMMON PLOTS
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
CROSSTALK vs FREQUENCY CMRR vs FREQUENCY
Figure 89. Figure 90.
POWER DISSIPATION vs SAMPLING FREQUENCY DRVDD CURRENT vs SAMPLING FREQUENCY
Figure 91. Figure 92.
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 53
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
20 50 150 200
f -InputFrequency-MHz
IN
f -SamplingFrequency-MSPS
S
SFDR-dBc
250 350 500
80
100
200
120
140
160
180
220
240
250
80
M0049-17
88
88
84
84
84
80
80
80
80
80
92
76
76
76
76
76
76
76
72
72
72 76
76
76
76
100 300
95
450400
70 9075 85
f -InputFrequency-MHz
IN
f -SamplingFrequency-MSPS
S
SFDR-dBc
80
100
200
120
140
160
180
220
240
250
75
M0049-18
88
88
88
88
88
85
85
85
85
91
82
82
82
82
79
79
79
79
79
79
79
75
75
75
71
71
71
67
67
63
63
67
9060 8565 8070
20 200 300 400 800100 500 700600
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
TYPICAL CHARACTERISTICS – ADS62P49/48/29/28
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SFDR CONTOUR, 0 dB GAIN, UP TO 500 MHz
Figure 93.
SFDR CONTOUR, 6 dB GAIN, UP TO 800 MHz
Figure 94.
54 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
20 50 150 200
f -InputFrequency-MHz
IN
f -SamplingFrequency-MSPS
S
SNR-dBFS
250 350 500
80
100
200
120
140
160
180
220
240
250
66 68
M0048-26
67
67
67
68
68
68
69
69
69
72
72
72
73
73
73
74
70
70
70
71
71
71
65
65
66
66
66
70
100 300
74
450400
64 72
20 200 300
f - Input Frequency - MHz
IN
f - Sampling Frequency - MSPS
S
SNR - dBFS
400 800
80
100
200
120
140
160
180
220
240
250
61 63
M0048-27
60 64 65
100 500
67 69
700600
62 66 68
61
61.5
61.5
61.5
62
62
62
62.5
62.5
62.5
63
63
63
63.5
63.5
63.5
64
64
64
64.5
64.5
64.5
65
65
65
65.5
65.5
65.5
66
66
66
66.5
66.5
66.5
67
67
67
68
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
TYPICAL CHARACTERISTICS – ADS62P49/48
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR CONTOUR, 0 dB GAIN, UP TO 500 MHz
Figure 95.
SNR CONTOUR, 6 dB GAIN, UP TO 800 MHz
Figure 96.
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Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
20 50 150 200
f -InputFrequency-MHz
IN
f -SamplingFrequency-MSPS
S
SNR-dBFS
250 350 500
80
100
200
120
140
160
180
220
240
250
65 67
M0048-28
66.5
66.5
66.5
66
66
66
69
69
69
70
70
70
71
71
68
68
68
67
67
67
65
65
65 64
65.5
65.5
65.5
64.5
64.5
68
100 300
71
450400
64 7066 69 72
SNR - dBFS
62 63
M0048-29
64 6861 666560 67
20 200 300
f - Input Frequency - MHz
IN
f - Sampling Frequency - MSPS
S
400 800
80
100
200
120
140
160
180
220
240
250
100 500 700600
61
61.5
61.5
61.5
62
62
62
62.5
62.5
62.5
63
63
63
63.5
63.5
63.5
64
64
64
64.5
64.5
64.5
65
65
65
65.5
65.5
65.5
66
66
66
66.5
66.5
66.5
67.5
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
TYPICAL CHARACTERISTICS – ADS62P29/28
All plots are at 25°C, AVDD = 3.3 V, DRVDD = 1.8 V, maximum rated sampling frequency, sine wave input clock. 1.5 VPP
differential clock amplitude, 50% clock duty cycle, –1 dBFS differential analog input, internal reference mode, 0 dB gain,
LVDS output interface, 32K point FFT (unless otherwise noted)
SNR CONTOUR, 0 dB GAIN, UP TO 500 MHz
Figure 97.
SNR CONTOUR, 6 dB GAIN, UP TO 800 MHz
Figure 98.
56 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
Resr
200 W
10 W
10 W
Sampling
Capacitor
Csamp
2pF
INP
INM
Cbond
1pF»
100 W
Cpar1
0.25pF
Ron
10 W
Cpar2
0.5pF
Ron
15 W
Ron
15 W
Cpar2
0.5pF
100 W
3pF
3pF
Lpkg 1nH»
Lpkg 1nH»
Cbond
1pF»Resr
200 W
Csamp
2pF
Sampling
Capacitor
Sampling
Switch
Sampling
Switch
RCRFilter
S0322-03
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
APPLICATION INFORMATION
THEORY OF OPERATION
The ADS62Px9/x8 is a family of high performance and low power dual channel 14-bit/12-bit A/D converters with
sampling rates up to 250 MSPS.
At every falling edge of the input clock, the analog input signal of each channel is sampled simultaneously. The
sampled signal in each channel is converted by a pipeline of low resolution stages. In each stage, the sampled
and held signal is converted by a high speed, low resolution flash sub-ADC. The difference (residue) between the
stage input and its quantized equivalent is gained and propagates to the next stage.
At every clock, each succeeding stage resolves the sampled input with greater accuracy. The digital outputs from
all stages are combined in a digital correction logic block and processed digitally to create the final code, after a
data latency of 22 clock cycles.
The digital output is available as either DDR LVDS or parallel CMOS and coded in either straight offset binary or
binary 2s complement format.
The dynamic offset of the first stage sub-ADC limits the maximum analog input frequency to about 500MHz (with
2V pp amplitude) and about 800MHz (with 1V pp amplitude).
ANALOG INPUT
The analog input consists of a switched-capacitor based differential sample and hold architecture. This
differential topology results in very good AC performance even for high input frequencies at high sampling rates.
The INP and INM pins have to be externally biased around a common-mode voltage of 1.5V, available on VCM
pin. For a full-scale differential input, each input pin INP, INM has to swing symmetrically between VCM + 0.5V
and VCM – 0.5V, resulting in a 2Vpp differential input swing.
The input sampling circuit has a high 3-dB bandwidth that extends up to 700 MHz (measured from the input pins
to the sampled voltage).
Figure 99. Analog Input Circuit
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0.01
0.10
1
10
100
0 100 200 300 400 500 600 700 800 900 1000
f - Frequency - MHz
R - Resistance - kW
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
Drive Circuit Requirements
For optimum performance, the analog inputs must be driven differentially. This improves the common-mode
noise immunity and even order harmonic rejection. A 5-Ωto 15-Ωresistor in series with each input pin is
recommended to damp out ringing caused by package parasitic.
SFDR performance can be limited due to several reasons - the effect of sampling glitches (described below),
non-linearity of the sampling circuit and non-linearity of the quantizer that follows the sampling circuit. Depending
on the input frequency, sample rate and input amplitude, one of these plays a dominant part in limiting
performance.
At very high input frequencies (> about 300 MHz), SFDR is determined largely by the device’s sampling circuit
non-linearity. At low input amplitudes, the quantizer non-linearity usually limits performance.
Glitches are caused by the opening and closing of the sampling switches. The driving circuit should present a
low source impedance to absorb these glitches. Otherwise, this could limit performance, mainly at low input
frequencies (up to about 200 MHz). It is also necessary to present low impedance (< 50 Ω) for the common
mode switching currents. This can be achieved by using two resistors from each input terminated to the common
mode voltage (VCM).
The device includes an internal R-C filter from each input to ground. The purpose of this filter is to absorb the
sampling glitches inside the device itself. The cut-off frequency of the R-C filter involves a trade-off. A lower
cut-off frequency (larger C) absorbs glitches better, but it reduces the input bandwidth. On the other hand, with a
higher cut-off frequency (smaller C), bandwidth support is maximized. But now, the sampling glitches need to be
supplied by the external drive circuit. This has limitations due to the presence of the package bond-wire
inductance.
In ADS62PXX, the R-C component values have been optimized while supporting high input bandwidth (up to 700
MHz). However, in applications with input frequencies up to 200-300MHz, the filtering of the glitches can be
improved further using an external R-C-R filter (as shown in Figure 102 and Figure 103).
In addition to the above, the drive circuit may have to be designed to provide a low insertion loss over the
desired frequency range and matched impedance to the source. While doing this, the ADC input impedance
must be considered. Figure 100 and Figure 101 show the impedance (Zin = Rin || Cin) looking into the ADC input
pins.
Figure 100. ADC Analog Input Resistance (Rin) Across Frequency
58 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
f − Frequency − MHz
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
0 100 200 300 400 500 600 700 800 900 1000
C − Capacitance − pF
G075
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
www.ti.com
SLAS635B –APRIL 2009–REVISED JANUARY 2011
Figure 101. ADC Analog Input Capacitance (Cin) Across Frequency
Driving Circuit
Two example driving circuit configurations are shown in Figure 102 and Figure 103 one optimized for low
bandwidth (low input frequencies) and the other one for high bandwidth to support higher input frequencies.
In Figure 102, an external R-C-R filter using 22 pF has been used. Together with the series inductor (39 nH), this
combination forms a filter and absorbs the sampling glitches. Due to the large capacitor (22 pF) in the R-C-R and
the 15-Ωresistors in series with each input pin, the drive circuit has low bandwidth and supports low input
frequencies (< 100MHz).
To support higher input frequencies (up to about 300 MHz, see Figure 103), the capacitance used in the R-C-R
is reduced to 3.3 pF and the series inductors are shorted out. Together with the lower series resistors (5 Ω), this
drive circuit provides high bandwidth and supports high input frequencies. Transformers such as ADT1-1WT or
ETC1-1-13 can be used up to 300MHz.
Without the external R-C-R filter, the drive circuit has very high bandwidth and can support very high input
frequencies (> 300MHz). For example, a transmission line transformer such as ADTL2-18 can be used (see
Figure 104).
Note that both the drive circuits have been terminated by 50 Ωnear the ADC side. The termination is
accomplished by a 25-Ωresistor from each input to the 1.5-V common-mode (VCM) from the device. This allows
the analog inputs to be biased around the required common-mode voltage.
The mismatch in the transformer parasitic capacitance (between the windings) results in degraded even-order
harmonic performance. Connecting two identical RF transformers back to back helps minimize this mismatch and
good performance is obtained for high frequency input signals. An additional termination resistor pair may be
required between the two transformers as shown in the figures. The center point of this termination is connected
to ground to improve the balance between the P and M side. The values of the terminations between the
transformers and on the secondary side have to be chosen to get an effective 50 Ω(in the case of 50-Ωsource
impedance).
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 59
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
INP
INM
VCM
15 W
25 W
25 W
15 W
50 W
50 W
0.1 Fm
22pF
0.1 Fm
39nH
39nH
0.1 Fm
S0396-01
1:1 1:1
0.1 Fm
50 W
50 W
INP
INM
VCM
5W
25 W
25 W
5W
0.1 Fm
3.3pF
0.1 Fm
0.1 Fm
S0397-01
1:1 1:1
0.1 Fm
50 W
50 W
INP
INM
VCM
0.1 Fm25 W
25 W
0.1 Fm
0.1 Fm
T1 T2
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
Figure 102. Drive Circuit With Low Bandwidth (for low input frequencies)
Figure 103. Drive Circuit With High Bandwidth (for high input frequencies)
Figure 104. Drive Circuit with Very High Bandwidth (> 300 MHz)
All these examples show 1:1 transformers being used with a 50-Ωsource. As explained in the “Drive Circuit
Requirements”, this helps to present a low source impedance to absorb the sampling glitches. With a 1:4
transformer, the source impedance will be 200 ohms. The higher impedance can lead to degradation in
performance, compared to the case with 1:1 transformers.
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INP
INM
VCM
1:4
5W
0.1 Fm
5W
100 W
100 W
25 W
25 W
15pF72nH
Differential
inputsignal
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
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SLAS635B –APRIL 2009–REVISED JANUARY 2011
For applications where only a band of frequencies are used, the drive circuit can be tuned to present a low
impedance for the sampling glitches. Figure 105shows an example with 1:4 transformer, tuned for a band around
150 MHz.
Figure 105. Drive Circuit with 1:4 Transformer
Input Common-Mode
To ensure a low-noise common-mode reference, the VCM pin is filtered with a 0.1mF low-inductance capacitor
connected to ground. The VCM pin is designed to directly drive the ADC inputs. The input stage of the ADC
sinks a common-mode current in the order of 3.6mA / MSPS (about 900mA at 250 MSPS).
REFERENCE
The ADS62Px9/x8 has built-in internal references REFP and REFM, requiring no external components. Design
schemes are used to linearize the converter load seen by the references; this and the on-chip integration of the
requisite reference capacitors eliminates the need for external decoupling. The full-scale input range of the
converter can be controlled in the external reference mode as explained below. The internal or external reference
modes can be selected by programming the serial interface register bit <REF>.
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S0165-09
VCM
REFM
REFP
INTREF
INTREF
EXTREF
Internal
Reference
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Figure 106. Reference Section
Internal Reference
When the device is in internal reference mode, the REFP and REFM voltages are generated internally.
Common-mode voltage (1.5V nominal) is output on VCM pin, which can be used to externally bias the analog
input pins.
External Reference
When the device is in external reference mode, the VCM acts as a reference input pin. The voltage forced on the
VCM pin is buffered and gained by 1.33 internally, generating the REFP and REFM voltages. The differential
input voltage corresponding to full-scale is given by the following:
Full-scale differential input pp = (Voltage forced on VCM) × 1.33
In this mode, the 1.5V common-mode voltage to bias the input pins has to be generated externally.
CLOCK INPUT
The ADS62Px9/x8 clock inputs can be driven differentially (sine, LVPECL or LVDS) or single-ended (LVCMOS),
with little or no difference in performance between them. The common-mode voltage of the clock inputs is set to
VCM using internal 5-kΩresistors as shown in Figure 107. This allows using transformer-coupled drive circuits
for sine wave clock or ac-coupling for LVPECL, LVDS clock sources (Figure 108,Figure 109, and Figure 110).
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CLKP
5 kW
VCM
5 kW
2 pF
20 W
20 W
CLKM
Clock Buffer
Ceq Ceq
Ceq 1 to 3 pF, Equivalent Input Capacitance of Clock Buffer»
Lpkg
2 nH»
Lpkg
2 nH»
Cbond
1 pF»
Cbond
1 pF»
Resr
100» W
Resr
100» W
S0275-04
CLKP
CLKM
0.1 Fm
0.1 Fm
100W
Typical LVDS
Clock Input
Zo
Zo
CLKP
CLKM
0.1 Fm
0.1 Fm
Differential Sine-wave
Clock Input RT
R = termination resistor if necessary
T
ADS62P49 / ADS62P29
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SLAS635B –APRIL 2009–REVISED JANUARY 2011
Figure 107. Internal Clock Buffer
Single-ended CMOS clock can be ac-coupled to the CLKP input, with CLKM (pin 11) connected to ground with a
0.1-mF capacitor, as shown in Figure 111.
For best performance, the clock inputs have to be driven differentially, reducing susceptibility to common-mode
noise. For high input frequency sampling, it is recommended to use a clock source with very low jitter. Bandpass
filtering of the clock source can help reduce the effect of jitter. There is no change in performance with a
non-50% duty cycle clock input.
Figure 108. Differential Sine-Wave Clock Driving Figure 109. Typical LVDS Clock Driving Circuit
Circuit
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CLKP
CLKM
0.1 Fm
0.1 Fm
100W
Typical LVPECL
Clock Input 150W
150W
Zo
Zo
CLKP
CLKM
0.1 Fm
0.1 Fm
CMOS Clock Input
VCM
ADS62P49 / ADS62P29
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Figure 110. Typical LVPECL Clock Driving Circuit Figure 111. Typical LVCMOS Clock Driving Circuit
GAIN PROGRAMMABILITY
The ADS62Px9/x8 includes gain settings that can be used to get improved SFDR performance (compared to no
gain). The gain is programmable from 0dB to 6dB (in 0.5 dB steps). For each gain setting, the analog input
full-scale range scales proportionally, as shown in Table 9.
The SFDR improvement is achieved at the expense of SNR; for each 1dB gain step, the SNR degrades about
1dB. The SNR degradation is less at high input frequencies. As a result, the gain is very useful at high input
frequencies as the SFDR improvement is significant with marginal degradation in SNR.
So, the gain can be used to trade-off between SFDR and SNR. Note that the default gain after reset is 0dB.
Table 9. Full-Scale Range Across Gains
GAIN, dB TYPE FULL-SCALE, Vpp
0 Default after reset 2 V
1 1.78
2 1.59
3 1.42
Fine, programmable
4 1.26
5 1.12
6 1.00
OFFSET CORRECTION
The ADS62Px9/x8 has an internal offset correction algorithm that estimates and corrects dc offset up to ±10mV.
The correction can be enabled using the serial register bit <ENABLE OFFSET CORRECTION>. Once enabled,
the algorithm estimates the channel offset and applies the correction every clock cycle. The time constant of the
correction loop is a function of the sampling clock frequency. The time constant can be controlled using register
bits <OFFSET CORR TIME CONSTANT> as described in Table 10.
After the offset is estimated, the correction can be frozen by setting <ENABLE OFFSET CORRECTION> back to
0.
Once frozen, the last estimated value is used for offset correction every clock cycle. The correction does not
affect the phase of the signal. Note that offset correction is disabled by default after reset.
Figure 112 shows the time response of the offset correction algorithm, after it is enabled.
Table 10. Time Constant of Offset Correction Algorithm
<OFFSET CORR TIME TIME CONSTANT (TCCLK), TIME CONSTANT, sec
CONSTANT> NUMBER OF CLOCK CYCLES (=TCCLK × 1/Fs) (1)
D3-D0
0000 256 k 1 ms
0001 512 k 2 ms
(1) Sampling frequency, Fs = 250 MSPS
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t − Time − ms
8155
8160
8165
8170
8175
8180
8185
8190
8195
8200
−2 0 2 4 6 8 10 12 14 16 18 20
Output Code − LSB
G076
Output Data With
Offset Corrected
Offset Correction Enabled
Output Data
With 34 LSB
Offset
Offset
Correction
Disabled
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SLAS635B –APRIL 2009–REVISED JANUARY 2011
Table 10. Time Constant of Offset Correction Algorithm (continued)
<OFFSET CORR TIME TIME CONSTANT (TCCLK), TIME CONSTANT, sec
CONSTANT> NUMBER OF CLOCK CYCLES (=TCCLK × 1/Fs) (1)
D3-D0
0010 1 M 4 ms
0011 2 M 8 ms
0100 4 M 17 ms
0101 8 M 33 ms
0110 16 M 67 ms
0111 32 M 134 ms
1000 64 M 268 ms
1001 128 M 536 ms
1010 256 M 1.1 s
1011 512 M 2.2 s
1100 RESERVED
1101 RESERVED
1110 RESERVED
1111 RESERVED
Figure 112. Time Response of Offset Correction
POWER DOWN
The ADS62Px9/x8 has two power down modes – global power down and individual channel standby. These can
be set using either the serial register bits or using the control pins CTRL1 to CTRL3.
CONFIGURE USING WAKE-UP
POWER DOWN MODES PARALLEL TIME
SERIAL INTERFACE CONTROL PINS
Normal operation <POWER DOWN MODES> = 0000 low low low –
Output buffer disabled for channel B <POWER DOWN MODES> = 1001 Not Available –
Output buffer disabled for channel A <POWER DOWN MODES> = 1010 Not Available –
Output buffer disabled for channel A and B <POWER DOWN MODES> = 1011 Not Available –
Global power down <POWER DOWN MODES> = 1100 high low low Slow (30 ms)
Channel B standby <POWER DOWN MODES> = 1101 high low high Fast (1 ms)
Channel A standby <POWER DOWN MODES> = 1110 high high low Fast (1 ms)
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CONFIGURE USING WAKE-UP
POWER DOWN MODES PARALLEL TIME
SERIAL INTERFACE CONTROL PINS
Multiplexed (MUX) mode – Output data of channel A <POWER DOWN MODES> = 1111 high high high –
and B is multiplexed and available on DA13 to DA0
pins.(1)
(1) Low Speed mode has to be enabled for Multiplexed Output mode (MUX mode). Therefore, MUX mode works with serial interface
configuration only and is not supported with parallel configuration.
Global Power Down
In this mode, the entire chip including both the A/D converters, internal reference and the output buffers are
powered down resulting in reduced total power dissipation of about 45 mW. The output buffers are in high
impedance state. The wake-up time from the global power down to data becoming valid in normal mode is
typically 30ms.
Channel Standby
Here, each channel’s A/D converter can be powered down. The internal references are active, resulting in quick
wake-up time of 1 ms. The total power dissipation in standby is about 475 mW.
Input Clock Stop
In addition to the above, the converter enters a low-power mode when the input clock frequency falls below 1
MSPS. The power dissipation is about 275 mW.
POWER SUPPLY SEQUENCE
During power-up, the AVDD and DRVDD supplies can come up in any sequence. The two supplies are
separated in the device. Externally, they can be driven from separate supplies or from a single supply.
DIGITAL OUTPUT INFORMATION
The ADS62Px9/x8 provides 14-bit/12-bit data and an output clock synchronized with the data.
Output Interface
Two output interface options are available – Double Data Rate (DDR) LVDS and parallel CMOS. They can be
selected using the serial interface register bit <LVDS_CMOS> or using DFS pin in parallel configuration mode.
DDR LVDS Outputs
In this mode, the data bits and clock are output using LVDS (Low Voltage Differential Signal) levels. Two data
bits are multiplexed and output on each LVDS differential pair.
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S0398-01
CLKOUTP
DB0_P
DB2_P
DB4_P
DB6_P
DB8_P
DB10_P
DB12_P
Pins
OutputClock
DataBitsD0,D1
DataBitsD2,D3
DataBitsD4,D5
DataBitsD6,D7
DataBitsD8,D9
DataBitsD10,D11
DataBitsD12,D13
CLKOUTM
DB0_M
DB2_M
DB4_M
DB6_M
DB8_M
DB10_M
DB12_M
ADS62P4x
14-Bit ADCChannel-BData
LVDSBuffers
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Figure 113. LVDS Outputs
Even data bits D0, D2, D4… are output at the rising edge of CLKOUTP and the odd data bits D1, D3, D5… are
output at the falling edge of CLKOUTP. Both the rising and falling edges of CLKOUTP have to be used to
capture all the data bits (see Figure 114).
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T0110-05
CLKOUTM
DA0,DB0
DA2,DB2
DA4,DB4
DA6,DB6
DA8,DB8
DA10,DB10
DA12,DB12
D0
D2
D4
D6
D8
D10
D12
SampleN+1SampleN
D0
D2
D4
D6
D8
D10
D12
D1
D3
D5
D7
D9
D11
D13
D1
D3
D5
D7
D9
D11
D13
CLKOUTP
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Figure 114. DDR LVDS Interface
LVDS Buffer
The equivalent circuit of each LVDS output buffer is shown in Figure 115. The buffer is designed to present an
output impedance of 100 Ω(Rout). The differential outputs can be terminated at the receive end by a 100-Ω
termination.
The buffer output impedance behaves like a source-side series termination. By absorbing reflections from the
receiver end, it helps to improve signal integrity. Note that this internal termination cannot be disabled and its
value cannot be changed.
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OUTP
OUTM
High
High Low
Low
ADS62P28/29/48/49
Rout
–0.35 V
1.2 V
0.35 V +
+
+
–
–
–
External
100- LoadW
Switch impedance is
nominally 50 ( 10%)W ±
When the High switches are closed, OUTP = 1.375 V, OUTM = 1.025 V
When the Low switches are closed, OUTP = 1.025 V, OUTM = 1.375 V
When the High (or Low) switches are closed, Rout = 100 W
S0374-03
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
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SLAS635B –APRIL 2009–REVISED JANUARY 2011
Figure 115. LVDS Buffer Equivalent Circuit
Parallel CMOS Interface
In CMOS mode, each data bit is output on a separate pin as a CMOS voltage level, every clock cycle. This mode
is recommended only up to 210 MSPS, beyond which the CMOS data outputs do not have sufficient time to
settle to valid logic levels.
For sampling frequencies up to 150 MSPS, the rising edge of the output clock CLKOUT can be used to latch
data in the receiver. The setup and hold timings of the output data with respect to CLKOUT are specified in the
timing specification table up to 150 MSPS.
For sampling frequencies above 150 MSPS, it is recommended to use an external clock to capture data. The
delay from input clock to output data and the data valid times are specified up to 210 MSPS. These timings can
be used to delay the input clock appropriately and use it to capture the data.
When using the CMOS interface, it is important to minimize the load capacitance seen by data and clock output
pins by using short traces on the board.
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S0399-01
CLKOUT
Pins
DA0
DB0
SDOUT
DA1
DB1
DA2
DB2
DA11
DB11
DA12
DB12
DA13
DB13
ADS62P49/48/29/28
14-Bit ADCChannel-A Data
14-Bit ADCChannel-BData
LVDSBuffers
·
·
·
·
·
·
·
·
·
·
·
·
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
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Figure 116. CMOS Outputs
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T0297-03
DA0
DA1
DA2
•
•
•
•
•
•
DA13
DB0
DB1
DB2
DB13
DB0
DB1
DB2
DB13
DA0
DA1
DA2
DA13
DA0
DA1
DA2
DA13
CLKOUT
SampleN+1SampleN
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CMOS Interface Power Dissipation
With CMOS outputs, the DRVDD current scales with the sampling frequency and the load capacitance on every
output pin. The maximum DRVDD current occurs when each output bit toggles between 0 and 1 every clock
cycle. In actual applications, this condition is unlikely to occur. The actual DRVDD current would be determined
by the average number of output bits switching, which is a function of the sampling frequency and the nature of
the analog input signal.
Digital current due to CMOS output switching = CL× DRVDD × (N × FAVG),
where
CL= load capacitance,
N × FAVG = average number of output bits switching.
Figure 92 shows the current with various load capacitances across sampling frequencies at 2.5-MHz analog
input frequency
Multiplexed Output Mode (only with CMOS interface)
In this mode, the digital outputs of both channels are multiplexed and output on a single bus (DA0-DA13 pins).
Channel B data bits are output at the rising edge of CLKOUT, and channel A data bits are output at the falling
edge of CLKOUT. The channel B output data pins (DB0-DB13) are 3-stated (see Figure 117 for details). Since
the output data rate on the DA bus is effectively doubled, this mode is recommended only for low sampling
frequencies (<65MSPS).
Low Speed mode has to be enabled for Multiplexed Output Mode (MUX mode). Therefore, MUX mode works
with serial interface configuration only and is not supported with parallel configuration. This mode can be enabled
using register bits <POWER DOWN MODES> or using the parallel pins CTRL1-3.
NOTES: 1. Both channel outputs are output on the channel A output data lines.
2. Channel A outputs are output on the falling edges whereas channel B outputs are output on the rising edges of
the output clock.
Figure 117. Multiplexed Output Mode Timing
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Output Data Format
Two output data formats are supported – 2s complement and offset binary. They can be selected using the serial
interface register bit <DATA FORMAT> or controlling the DFS pin in parallel configuration mode.
In the event of an input voltage overdrive, the digital outputs go to the appropriate full scale level. For a positive
overdrive, the output code is 0x3FFF in offset binary output format, and 0x1FFF in 2s complement output format.
For a negative input overdrive, the output code is 0x0000 in offset binary output format and 0x2000 in 2s
complement output format.
BOARD DESIGN CONSIDERATIONS
Grounding
A single ground plane is sufficient to give good performance, provided the analog, digital, and clock sections of
the board are cleanly partitioned. See the EVM User Guide (SLAU237) for details on layout and grounding.
Supply Decoupling
As ADS62Px9/x8 already includes internal decoupling, minimal external decoupling can be used without loss in
performance. Note that decoupling capacitors can help filter external power supply noise, so the optimum
number of capacitors would depend on the actual application. The decoupling capacitors should be placed very
close to the converter supply pins.
Exposed Pad
In addition to providing a path for heat dissipation, the pad is also electrically connected to digital ground
internally. So, it is necessary to solder the exposed pad to the ground plane for best thermal and electrical
performance. For detailed information, see application notes QFN Layout Guidelines (SLOA122) and QFN/SON
PCB Attachment (SLUA271).
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10 S
N
P
SNR = 10Log P
10 S
N D
P
SINAD = 10Log P + P
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SLAS635B –APRIL 2009–REVISED JANUARY 2011
DEFINITION OF SPECIFICATIONS
Analog Bandwidth – The analog input frequency at which the power of the fundamental is reduced by 3 dB with
respect to the low frequency value.
Aperture Delay – The delay in time between the rising edge of the input sampling clock and the actual time at
which the sampling occurs. This delay will be different across channels. The maximum variation is specified as
aperture delay variation (channel-channel).
Aperture Uncertainty (Jitter) – The sample-to-sample variation in aperture delay.
Clock Pulse Width/Duty Cycle – The duty cycle of a clock signal is the ratio of the time the clock signal remains
at a logic high (clock pulse width) to the period of the clock signal. Duty cycle is typically expressed as a
percentage. A perfect differential sine-wave clock results in a 50% duty cycle.
Maximum Conversion Rate – The maximum sampling rate at which certified operation is given. All parametric
testing is performed at this sampling rate unless otherwise noted.
Minimum Conversion Rate – The minimum sampling rate at which the ADC functions.
Differential Nonlinearity (DNL) – An ideal ADC exhibits code transitions at analog input values spaced exactly
1 LSB apart. The DNL is the deviation of any single step from this ideal value, measured in units of LSBs.
Integral Nonlinearity (INL) – The INL is the deviation of the ADC's transfer function from a best fit line
determined by a least squares curve fit of that transfer function, measured in units of LSBs.
Gain Error – Gain error is the deviation of the ADC's actual input full-scale range from its ideal value. The gain
error is given as a percentage of the ideal input full-scale range. Gain error has two components: error due to
reference inaccuracy and error due to the channel. Both these errors are specified independently as EGREF and
EGCHAN.
To a first order approximation, the total gain error will be ETOTAL ~ EGREF + EGCHAN.
For example, if ETOTAL = ±0.5%, the full-scale input varies from (1-0.5/100) x FSideal to (1 + 0.5/100) x FSideal.
Offset Error – The offset error is the difference, given in number of LSBs, between the ADC's actual average
idle channel output code and the ideal average idle channel output code. This quantity is often mapped into mV.
Temperature Drift – The temperature drift coefficient (with respect to gain error and offset error) specifies the
change per degree Celsius of the parameter from TMIN to TMAX. It is calculated by dividing the maximum deviation
of the parameter across the TMIN to TMAX range by the difference TMAX–TMIN.
Signal-to-Noise Ratio – SNR is the ratio of the power of the fundamental (PS) to the noise floor power (PN),
excluding the power at DC and the first nine harmonics.
(1)
SNR is either given in units of dBc (dB to carrier) when the absolute power of the fundamental is used as the
reference, or dBFS (dB to full scale) when the power of the fundamental is extrapolated to the converter’s
full-scale range.
Signal-to-Noise and Distortion (SINAD) – SINAD is the ratio of the power of the fundamental (PS) to the power
of all the other spectral components including noise (PN) and distortion (PD), but excluding dc.
(2)
SINAD is either given in units of dBc (dB to carrier) when the absolute power of the fundamental is used as the
reference, or dBFS (dB to full scale) when the power of the fundamental is extrapolated to the converter's
full-scale range.
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SINAD 1.76
ENOB =
6.02
-
10 S
N
P
THD = 10Log P
(ExpressedindBc)
DVSUP
DVOUT
10
PSRR=20Log
(ExpressedindBc)
DVCM
DVOUT
10
CMRR=20Log
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Effective Number of Bits (ENOB) – The ENOB is a measure of the converter performance as compared to the
theoretical limit based on quantization noise.
(3)
Total Harmonic Distortion (THD) – THD is the ratio of the power of the fundamental (PS) to the power of the
first nine harmonics (PD).
(4)
THD is typically given in units of dBc (dB to carrier).
Spurious-Free Dynamic Range (SFDR) – The ratio of the power of the fundamental to the highest other
spectral component (either spur or harmonic). SFDR is typically given in units of dBc (dB to carrier).
Two-Tone Intermodulation Distortion – IMD3 is the ratio of the power of the fundamental (at frequencies f1
and f2) to the power of the worst spectral component at either frequency 2f1–f2 or 2f2–f1. IMD3 is either given in
units of dBc (dB to carrier) when the absolute power of the fundamental is used as the reference, or dBFS (dB to
full scale) when the power of the fundamental is extrapolated to the converter’s full-scale range.
DC Power Supply Rejection Ratio (DC PSRR) – The DC PSSR is the ratio of the change in offset error to a
change in analog supply voltage. The DC PSRR is typically given in units of mV/V.
AC Power Supply Rejection Ratio (AC PSRR) – AC PSRR is the measure of rejection of variations in the
supply voltage by the ADC. If ΔVSUP is the change in supply voltage and ΔVout is the resultant change of the
ADC output code (referred to the input), then
(5)
Voltage Overload Recovery – The number of clock cycles taken to recover to less than 1% error after an
overload on the analog inputs. This is tested by separately applying a sine wave signal with 6dB positive and
negative overload. The deviation of the first few samples after the overload (from their expected values) is noted.
Common Mode Rejection Ratio (CMRR) – CMRR is the measure of rejection of variation in the analog input
common-mode by the ADC. If ΔVcm_in is the change in the common-mode voltage of the input pins and ΔVOUT
is the resultant change of the ADC output code (referred to the input), then
(6)
Cross-Talk (only for multi-channel ADC)– This is a measure of the internal coupling of a signal from adjacent
channel into the channel of interest. It is specified separately for coupling from the immediate neighboring
channel (near-channel) and for coupling from channel across the package (far-channel). It is usually measured
by applying a full-scale signal in the adjacent channel. Cross-talk is the ratio of the power of the coupling signal
(as measured at the output of the channel of interest) to the power of the signal applied at the adjacent channel
input. It is typically expressed in dBc.
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SLAS635B –APRIL 2009–REVISED JANUARY 2011
REVISION HISTORY
Changes from Original (April 2009) to Revision A Page
• Changed ADS62P48, ADS62P29, ADS62P28 from product preview to production data .................................................... 4
• Added Analog supply current max value of 320 mA ............................................................................................................ 7
• Added Output buffer supply current, LVDS interface max value of 165 mA ........................................................................ 7
• Added Analog power max value of 1.05 W .......................................................................................................................... 7
• Added Digital power, LVDS interface max value of 0.3 W ................................................................................................... 7
• Added SNR Signal to noise ratio,LVDS, Fin = 170 MHz, 0 dB gain min value of 68 dBFS ................................................. 8
• Added SINADSignal to noise and distortion ratio, LVDS, Fin = 170 MHz, 0 dB gain min value of 66.5 dBFS ................... 8
• Added SNR Signal to noise ratio,LVDS, Fin = 170 MHz, 0 dB gain min value of 66.5 dBFS .............................................. 8
• Added SNR Signal to noise ratio,LVDS, Fin = 170 MHz, 0 dB gain min value of 66.5 dBFS .............................................. 8
• Added SINADSignal to noise and distortion ratio, LVDS, Fin = 170 MHz, 0 dB gain min value of 66 dBFS ...................... 8
• Added SINADSignal to noise and distortion ratio, LVDS, Fin = 170 MHz, 0 dB gain min value of 66 dBFS ...................... 8
• Added DNL Differential non-linearity min value of –0.9 LSB ................................................................................................ 8
• Added DNL Differential non-linearity max value of 1.3 LSB ................................................................................................. 8
• Added DNL Differential non-linearity min value of –0.9 LSB ................................................................................................ 8
• Added DNL Differential non-linearity max value of 1.3 LSB ................................................................................................. 8
• Added INL Integrated non-linearity min value of –5 LSB ..................................................................................................... 8
• Added INL Integrated non-linearity max value of 5 LSB ...................................................................................................... 8
• Added INL Integrated non-linearity min value of –5 LSB ..................................................................................................... 8
• Added INL Integrated non-linearity max value of 5 LSB ...................................................................................................... 8
• Added SFDR Spurious Free Dynamic Range, Fin = 170 MHz min value of 71 dBc ........................................................... 9
• Added SFDRSpurious Free Dynamic Range, excluding HD2,HD3, Fin = 170 MHz min value of 78 dBc ........................... 9
• Added HD2 Second Harmonic Distortion, Fin = 170 MHz min value of 71 dBc ................................................................... 9
• Added HD3 Third Harmonic Distortion, Fin = 170 MHz min value of 71 dBc ....................................................................... 9
• Added THDTotal harmonic distortion, Fin = 170 MHz min value of 70.5 dBc ...................................................................... 9
• Added IMD2-Tone Inter-modulation Distortion, F1 = 46 MHz, F2 = 50 MHz, each tone at –7 dBFS typ value of 91
dBFS ..................................................................................................................................................................................... 9
Changes from Revision A (June 2009) to Revision B Page
• Changed Voltage between AVDD to DRVDD in ABSOLUTE MAXIMUM RATINGS ........................................................... 4
• Changed Voltage between DRVDD to AVDD in ABSOLUTE MAXIMUM RATINGS ........................................................... 4
• Added new thermal table ...................................................................................................................................................... 6
• Added table note 2 ................................................................................................................................................................ 6
• Added table notes 5 and 6 and Figure 3 .............................................................................................................................. 6
• Changed Sine wave, ac-coupled, TYP from 3 to 1.5 VPP ..................................................................................................... 6
• Added Figure 3 ..................................................................................................................................................................... 6
• Changed Digital Characteristics - ADS62Px9/x8 table note 2 ............................................................................................ 10
• Added table note to Timing Requirements table in row tOE ................................................................................................ 12
• Added table note 1 to Table 2 and Table 3 ........................................................................................................................ 12
• Added for Fs ≤80 to Table 2 and Table 3 .......................................................................................................................... 12
• Changed To put the device in parallel configuration mode, keep RESET tied to high (AVDD). to To put the device in
parallel configuration mode, keep RESET tied to high (AVDD or DRVDD). in PARALLEL CONFIGURATION ONLY
section ................................................................................................................................................................................. 15
• Changed Table 4 ................................................................................................................................................................ 15
Copyright © 2009–2011, Texas Instruments Incorporated Submit Documentation Feedback 75
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
ADS62P49 / ADS62P29
ADS62P48 / ADS62P28
SLAS635B –APRIL 2009–REVISED JANUARY 2011
www.ti.com
• Deleted 2 in Table 5 ............................................................................................................................................................ 15
• Changed Table 6 ................................................................................................................................................................ 16
• Added note to Table 7 and changed rows to Not available ................................................................................................ 16
• Changed sampling frequency from 100 MSPS to 80 MSPS in serial register 20 .............................................................. 22
• Added 00 and 10 to D6-D5 of serial register 3F ................................................................................................................. 22
• Added reference to the Multiplexed Output Mode section in the APPLICATION INFORMATION .................................... 22
• Changed Serial register 44 description ............................................................................................................................... 23
• Added Figure 12 ................................................................................................................................................................. 24
• Added Figure 13 ................................................................................................................................................................. 24
• Added information to serial register 62 D2-D0 test patterns .............................................................................................. 27
• Added Figure 14 ................................................................................................................................................................. 28
• Added Figure 15 ................................................................................................................................................................. 29
• Added Figure 16 ................................................................................................................................................................. 30
• Added information to serial register 75 D2-D0 test patterns .............................................................................................. 33
• Changed DRVDD to AVDD in Pin Assignments (LVDS MODE) pin 15 description .......................................................... 37
• Added to Pin Assignments (LVDS MODE) pin 37 description ........................................................................................... 37
• Deleted true from DA and DB descriptions in Pin Assignments (LVDS MODE) ................................................................ 37
• Changed SDATA to SCLK in Pin Assignments (CMOS MODE) pin 12 description .......................................................... 40
• Changed DRVDD to AVDD in Pin Assignments (CMOS MODE) pin 15 description ......................................................... 40
• Added to Pin Assignments (CMOS MODE) pin 37 description .......................................................................................... 40
• Changed CMSO mode CLKOUT pin number from 5 to 57 ................................................................................................ 40
• Changed Figure 96 ............................................................................................................................................................. 55
• Changed Figure 98 ............................................................................................................................................................. 56
• Changed Figure 108 ........................................................................................................................................................... 63
• Changed Figure 109 ........................................................................................................................................................... 63
• Added Figure 110 ............................................................................................................................................................... 63
• Added Figure 111 ............................................................................................................................................................... 63
• Changed Power Down Modes table and added note ......................................................................................................... 65
• Changed Figure 115 ........................................................................................................................................................... 69
• Added Multiplexed Output Mode (only with CMOS interface) section information ............................................................. 71
76 Submit Documentation Feedback Copyright © 2009–2011, Texas Instruments Incorporated
Product Folder Link(s): ADS62P49 / ADS62P29 ADS62P48 / ADS62P28
PACKAGE OPTION ADDENDUM
www.ti.com 8-Jul-2010
Addendum-Page 1
PACKAGING INFORMATION
Orderable Device Status (1) Package Type Package
Drawing Pins Package Qty Eco Plan (2) Lead/
Ball Finish MSL Peak Temp (3) Samples
(Requires Login)
ADS62P28IRGC25 ACTIVE VQFN RGC 64 25 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P28IRGCR ACTIVE VQFN RGC 64 2000 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P28IRGCT ACTIVE VQFN RGC 64 250 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P29IRGC25 ACTIVE VQFN RGC 64 25 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P29IRGCR ACTIVE VQFN RGC 64 2000 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P29IRGCT ACTIVE VQFN RGC 64 250 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P48IRGC25 ACTIVE VQFN RGC 64 25 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P48IRGCR ACTIVE VQFN RGC 64 2000 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P48IRGCT ACTIVE VQFN RGC 64 250 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P49IRGC25 ACTIVE VQFN RGC 64 25 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P49IRGCR ACTIVE VQFN RGC 64 2000 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
ADS62P49IRGCT ACTIVE VQFN RGC 64 250 Green (RoHS
& no Sb/Br) CU NIPDAU Level-3-260C-168 HR
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
PACKAGE OPTION ADDENDUM
www.ti.com 8-Jul-2010
Addendum-Page 2
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device Package
Type Package
Drawing Pins SPQ Reel
Diameter
(mm)
Reel
Width
W1 (mm)
A0
(mm) B0
(mm) K0
(mm) P1
(mm) W
(mm) Pin1
Quadrant
ADS62P28IRGCR VQFN RGC 64 2000 330.0 16.4 9.3 9.3 1.5 12.0 16.0 Q2
ADS62P28IRGCT VQFN RGC 64 250 330.0 16.4 9.3 9.3 1.5 12.0 16.0 Q2
ADS62P29IRGCR VQFN RGC 64 2000 330.0 16.4 9.3 9.3 1.5 12.0 16.0 Q2
ADS62P29IRGCT VQFN RGC 64 250 330.0 16.4 9.3 9.3 1.5 12.0 16.0 Q2
ADS62P48IRGCR VQFN RGC 64 2000 330.0 16.4 9.3 9.3 1.5 12.0 16.0 Q2
ADS62P48IRGCT VQFN RGC 64 250 330.0 16.4 9.3 9.3 1.5 12.0 16.0 Q2
ADS62P49IRGCR VQFN RGC 64 2000 330.0 16.4 9.3 9.3 1.5 12.0 16.0 Q2
ADS62P49IRGCT VQFN RGC 64 250 330.0 16.4 9.3 9.3 1.5 12.0 16.0 Q2
PACKAGE MATERIALS INFORMATION
www.ti.com 3-Sep-2012
Pack Materials-Page 1
*All dimensions are nominal
Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm)
ADS62P28IRGCR VQFN RGC 64 2000 336.6 336.6 28.6
ADS62P28IRGCT VQFN RGC 64 250 336.6 336.6 28.6
ADS62P29IRGCR VQFN RGC 64 2000 336.6 336.6 28.6
ADS62P29IRGCT VQFN RGC 64 250 336.6 336.6 28.6
ADS62P48IRGCR VQFN RGC 64 2000 336.6 336.6 28.6
ADS62P48IRGCT VQFN RGC 64 250 336.6 336.6 28.6
ADS62P49IRGCR VQFN RGC 64 2000 336.6 336.6 28.6
ADS62P49IRGCT VQFN RGC 64 250 336.6 336.6 28.6
PACKAGE MATERIALS INFORMATION
www.ti.com 3-Sep-2012
Pack Materials-Page 2
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