Features
Low nonlinearity: 0.01%
K
3 (IPD2/IPD1) transfer gain
HCNR200: ±15%
HCNR201: ±5%
Low gain temperature coe cient: -65 ppm/°C
Wide bandwidth – DC to >1 MHz
Worldwide safety approval
– UL 1577 recognized (5 kV rms/1 min rating)
– CSA approved
– IEC/EN/DIN EN 60747-5-2 approved
V
IORM = 1414 V peak (option #050)
Surface mount option available (Option #300)
8-Pin DIP package - 0.400” spacing
Allows exible circuit design
Applications
Low cost analog isolation
Telecom: Modem, PBX
Industrial process control:
Transducer isolator
Isolator for thermo couples 4 mA to 20 mA loop isola-
tion
SMPS feedback loop, SMPS feedforward
Monitor motor supply voltage
Medical
Description
The HCNR200/201 high-linearity analog optocoupler
consists of a high-performance AlGaAs LED that illumi-
nates two closely matched photodiodes. The input pho-
todiode can be used to monitor, and therefore stabilize,
the light output of the LED. As a result, the non-linearity
and drift characteristics of the LED can be virtually elimi-
nated. The output photodiode produces a photocur rent
that is linearly related to the light output of the LED. The
close matching of the photo-diodes and advanced de-
sign of the package ensure the high linearity and stable
gain characteristics of the opto coupler.
The HCNR200/201 can be used to isolate analog signals
in a wide variety of applications that require good stabil-
ity, linearity, bandwidth and low cost. The HCNR200/201
is very exible and, by appro priate design of the appli-
cation circuit, is capable of operating in many di erent
modes, includ ing: unipolar/bipolar, ac/dc and inverting/
non-inverting. The HCNR200/201 is an excellent solution
for many analog isola tion problems.
Schematic
HCNR200 and HCNR201
High-Linearity Analog Optocouplers
Data Sheet
CAUTION: It is advised that normal static precautions be taken in handling and assembly
of this component to prevent damage and/or degradation which may be induced by ESD.
Lead (Pb) Free
RoHS 6 fully
compliant
RoHS 6 fully compliant options available;
-xxxE denotes a lead-free product
3
4
1
2
V
F
-
+I
F
I
PD1
6
5
I
PD2
8
7
NC
NC
PD2 CATHODE
PD2 ANODE
LED CATHODE
LED ANODE
PD1 CATHODE
PD1 ANODE
2
Ordering Information
HCNR200/HCNR201 is UL Recognized with 5000 Vrms for 1 minute per UL1577.
Option IEC/EN/DIN EN
Part RoHS non RoHS Surface Gull Tape UL 5000 Vrms/ 60747-5-2
Number Compliant Compliant Package Mount Wing & Reel 1 Minute rating
VIORM = 1414 Vpeak
Quantity
-000E no option 400 mil X 42 per tube
-300E #300 Widebody X X X 42 per tube
HCNR200
-500E #500 DIP-8 X X X X 750 per reel
HCNR201
-050E #050 X X 42 per tube
-350E #350 X X X X 42 per tube
-550E #550 X X X X X 750 per reel
To order, choose a part number from the part number column and combine with the desired option from the option
column to form an order entry.
Example 1:
HCNR200-550E to order product of Gull Wing Surface Mount package in Tape and Reel packaging with IEC/EN/
DIN EN 60747-5-2 VIORM = 1414 Vpeak Safety Approval and UL 5000 Vrms for 1 minute rating and RoHS compliant.
Example 2:
HCNR201 to order product of 8-Pin Widebody DIP package in Tube packaging with UL 5000 Vrms for 1 minute rating
and non RoHS compliant.
Option datasheets are available. Contact your Avago sales representative or authorized distributor for information.
Remarks: The notation ‘#XXX’ is used for existing products, while (new) products launched since July 15, 2001 and
RoHS compliant will use ‘–XXXE.’
3
Package Outline Drawings
Figure 1a. 8 PIN DIP
0.40 (0.016)
0.56 (0.022)
1
2
3
4
8
7
6
5
1.70 (0.067)
1.80 (0.071)
2.54 (0.100) TYP.
0.51 (0.021) MIN.
5.10 (0.201) MAX.
3.10 (0.122)
3.90 (0.154)
DIMENSIONS IN MILLIMETERS AND (INCHES).
MARKING :
XXX = 050 ONLY if option #050,#350,#550 (or -050,-350,-550)
ordered (otherwise blank)
yy - Year
ww - Work Week
Marked with black dot - Designates Lead Free option E
* - Designates pin 1
NOTE: FLOATING LEAD PROTRUSION IS 0.25 mm (10 mils) MAX.
NC
PD1
K1
11.30 (0.445)
MAX.
PIN
ONE 1.50
(0.059)
MAX.
A
HCNR200
XXX
yyww
MARKING
8 7 6 5
12 3 4
9.00
(0.354)
TYP.
0.20 (0.008)
0.30 (0.012)
0°
15°
11.00
(0.433)
MAX.
10.16
(0.400)
TYP.
K2
PD2
NC
LED
z
*
4
Gull Wing Surface Mount Option #300
1.00 ± 0.15
(0.039 ± 0.006)
7° NOM.
12.30 ± 0.30
(0.484 ± 0.012)
0.75 ± 0.25
(0.030 ± 0.010)
11.00
(0.433)
5
6
7
8
4
3
2
1
11.15 ± 0.15
(0.442 ± 0.006)
9.00 ± 0.15
(0.354 ± 0.006)
1.3
(0.051)
13.56
(0.534)
2.29
(0.09)
LAND PATTERN RECOMMENDATION
1.78 ± 0.15
(0.070 ± 0.006)
4.00
(0.158)MAX.
1.55
(0.061)
MAX.
2.54
(0.100)
BSC
DIMENSIONS IN MILLIMETERS (INCHES).
LEAD COPLANARITY = 0.10 mm (0.004 INCHES).
NOTE: FLOATING LEAD PROTRUSION IS 0.25 mm (10 mils) MAX.
0.254 + 0.076
- 0.0051
(0.010+ 0.003)
- 0.002)
MAX.
Figure 1b. 8 PIN Gull Wing Surface Mount Option #300
5
Solder Re ow Temperature Pro le
Regulatory Information
The HCNR200/201 optocoupler features a 0.400” wide, eight pin DIP package. This package was speci cally designed
to meet worldwide regulatory require ments. The HCNR200/201 has been approved by the following organizations:
Recommended Pb-Free IR Pro le
0
TIME (SECONDS)
TEMPERATURE (°C)
200
100
50 150100 200 250
300
0
30
SEC.
50 SEC.
30
SEC.
160 °C
140 °C
150 °C
PEAK
TEMP.
245 °C
PEAK
TEMP.
240 °CPEAK
TEMP.
230 °C
SOLDERING
TIME
200 °C
PREHEATING TIME
150 °C, 90 + 30 SEC.
2.5 C ± 0.5 °C/SEC.
3 °C + 1 °C/–0.5 °C
TIGHT
TYPICAL
LOOSE
ROOM
TEMPERATURE
PREHEATING RATE 3 °C + 1 °C/–0.5 °C/SEC.
REFLOW HEATING RATE 2.5 °C ± 0.5 °C/SEC.
NOTE: NON-HALIDE FLUX SHOULD BE USED.
217 °C
RAMP-DOWN
6 °C/SEC. MAX.
RAMP-UP
3 °C/SEC. MAX.
150 - 200 °C
* 245 +0/-5 °C
t 25 °C to PEAK
60 to 150 SEC.
15 SEC.
TIME WITHIN 5 °C of ACTUAL PEAK TEMPERATURE
tp
ts
PREHEAT
60 to 180 SEC.
tL
TL
Tsmax
Tsmin
25
Tp
TIME
TEMPERATURE
NOTES:
THE TIME FROM 25 °C to PEAK
TEMPERATURE = 8 MINUTES MAX.
Tsmax = 200 °C, Tsmin = 150 °C
NOTE: NON-HALIDE FLUX SHOULD BE USED.
UL
Recognized under UL 1577, Component Recognition
Program, FILE E55361
CSA
Approved under CSA Component Acceptance Notice
#5, File CA 88324
IEC/EN/DIN EN 60747-5-2
Approved under
IEC 60747-5-2:1997 + A1:2002
EN 60747-5-2:2001 + A1:2002
DIN EN 60747-5-2 (VDE 0884 Teil 2):2003-01
(Option 050 only)
6
Insulation and Safety Related Speci cations
Parameter Symbol Value Units Conditions
Min. External Clearance L(IO1) 9.6 mm Measured from input terminals to output
(External Air Gap) terminals, shortest distance through air
Min. External Creepage L(IO2) 10.0 mm Measured from input terminals to output
(External Tracking Path) terminals, shortest distance path along body
Min. Internal Clearance 1.0 mm Through insulation distance conductor to
(Internal Plastic Gap) conductor, usually the direct distance
between the photoemitter and photodetector
inside the optocoupler cavity
Min. Internal Creepage 4.0 mm The shortest distance around the border
(Internal Tracking Path) between two di erent insulating materials
measured between the emitter and detector
Comparative Tracking Index CTI 200 V DIN IEC 112/VDE 0303 PART 1
Isolation Group IIIa Material group (DIN VDE 0110)
Option 300 – surface mount classi cation is Class A in accordance with CECC 00802.
IEC/EN/DIN EN 60747-5-2 Insulation Characteristics (Option #050 Only)
Description Symbol Characteristic Unit
Installation classi cation per DIN VDE 0110/1.89, Table 1
For rated mains voltage ≤600 V rms I-IV
For rated mains voltage ≤1000 V rms I-III
Climatic Classi cation (DIN IEC 68 part 1) 55/100/21
Pollution Degree (DIN VDE 0110 Part 1/1.89) 2
Maximum Working Insulation Voltage VIORM 1414 V
peak
Input to Output Test Voltage, Method b* VPR 2651 V
peak
V
PR = 1.875 x VIORM, 100% Production Test with
tm = 1 sec, Partial Discharge < 5 pC
Input to Output Test Voltage, Method a* VPR 2121 V
peak
V
PR = 1.5 x VIORM, Type and sample test, tm = 60 sec,
Partial Discharge < 5 pC
Highest Allowable Overvoltage* VIOTM 8000 V
peak
(Transient Overvoltage, tini = 10 sec)
Safety-Limiting Values
(Maximum values allowed in the event of a failure,
also see Figure 11)
Case Temperature TS 150 °C
Current (Input Current IF, PS = 0) IS 400 mA
Output Power PS,OUTPUT 700 mW
Insulation Resistance at TS, VIO = 500 V RS >109 Ω
*Refer to the front of the Optocoupler section of the current catalog for a more detailed description of IEC/EN/DIN EN 60747-5-2 and other prod-
uct safety regulations.
Note: Optocouplers providing safe electrical separation per IEC/EN/DIN EN 60747-5-2 do so only within the safety-limiting values to which they
are quali ed. Protective cut-out switches must be used to ensure that the safety limits are not exceeded.
7
Absolute Maximum Ratings
Storage Temperature ..............................................................................................-55°C to +125°C
Operating Temperature (T
A) ................................................................................. -55°C to +100°C
Junction Temperature (TJ) ......................................................................................................... 125°C
Re ow Temperature Pro le ..............................................See Package Outline Drawings Section
Lead Solder Temperature ............................................................................................260°C for 10s
(up to seating plane)
Average Input Current - IF ........................................................................................................ 25 mA
Peak Input Current - IF ............................................................................................................... 40 mA
(50 ns maximum pulse width)
Reverse Input Voltage - VR ............................................................................................................2.5 V
(IR = 100 μA, Pin 1-2)
Input Power Dissipation ....................................................................................60 mW @ T
A = 85°C
(Derate at 2.2 mW/°C for operating temperatures above 85°C)
Reverse Output Photodiode Voltage ........................................................................................30 V
(Pin 6-5)
Reverse Input Photodiode Voltage ............................................................................................30 V
(Pin 3-4)
Recommended Operating Conditions
Storage Temperature .................................................................................................-40°C to +85°C
Operating Temperature ............................................................................................-40°C to +85°C
Average Input Current - IF .................................................................................................. 1 - 20 mA
Peak Input Current - IF ............................................................................................................... 35 mA
(50% duty cycle, 1 ms pulse width)
Reverse Output Photodiode Voltage ..................................................................................0 - 15 V
(Pin 6-5)
Reverse Input Photodiode Voltage ......................................................................................0 - 15 V
(Pin 3-4)
8
Electrical Speci cations
T
A = 25°C unless otherwise speci ed.
Parameter Symbol Device Min. Typ. Max. Units Test Conditions Fig. Note
Transfer Gain K3 HCNR200 0.85 1.00 1.15 5 nA < IPD < 50 μA, 2,3 1
0 V < VPD < 15 V
HCNR201 0.95 1.00 1.05 5 nA < IPD < 50 μA, 1
0 V < VPD < 15 V
HCNR201 0.93 1.00 1.07 -40°C < T
A < 85°C, 1
5 nA < IPD < 50 μA,
0 V < VPD < 15 V
Temperature ΔK3/ΔT
A -65 ppm/°C -40°C < T
A < 85°C, 2,3
Coe cient of 5 nA < IPD < 50 μA,
Transfer Gain 0 V < VPD < 15 V
DC NonLinearity NLBF HCNR200 0.01 0.25 % 5 nA < IPD < 50 μA, 4,5, 2
(Best Fit) 0 V < VPD < 15 V 6
HCNR201 0.01 0.05 5 nA < IPD < 50 μA, 2
0 V < VPD < 15 V
HCNR201 0.01 0.07 -40°C < T
A < 85°C, 2
5 nA < IPD < 50 μA,
0 V < VPD < 15 V
DC Nonlinearity NLEF 0.016 5 nA < IPD < 50 μA, 3
(Ends Fit) % 0 V < VPD < 15 V
Input Photo- K1 HCNR200 0.25 0.50 0.75 % IF = 10 mA, 7
diode Current 0 V < VPD1 < 15 V
Transfer Ratio HCNR201 0.36 0.48 0.72
(IPD1/IF)
Temperature ΔK1/ΔT
A -0.3 %/°C -40°C < T
A < 85°C, 7
Coe cient IF = 10 mA
of K1 0 V < VPD1 < 15 V
Photodiode ILK 0.5 25 nA IF = 0 mA, 8
Leakage Current 0 V < VPD < 15 V
Photodiode BVRPD 30 150 V IR = 100 μA
Reverse Break-
down Voltage
Photodiode CPD 22 pF VPD = 0 V
Capacitance
LED Forward VF 1.3 1.6 1.85 V IF = 10 mA 9,
Voltage 10
1.2 1.6 1.95 IF = 10 mA,
-40°C < T
A < 85°C
LED Reverse BVR 2.5 9 V IF = 100 μA
Breakdown
Voltage
Temperature ΔV
F/ΔT
A -1.7 mV/°C IF = 10 mA
Coe cient of
Forward Voltage
LED Junction CLED 80 pF f = 1 MHz,
Capacitance V
F = 0 V
9
AC Electrical Speci cations
T
A = 25°C unless otherwise speci ed.
Test
Parameter Symbol Device Min. Typ. Max. Units Conditions Fig. Note
LED Bandwidth f -3dB 9 MHz IF = 10 mA
Application Circuit Bandwidth:
High Speed 1.5 MHz 16 6
High Precision 10 kHz 17 6
Application Circuit: IMRR
High Speed 95 dB freq = 60 Hz 16 6, 7
Notes:
1. K3 is calculated from the slope of the best t line of IPD2 vs. IPD1 with eleven equally distributed data points from 5 nA to 50 μA. This is approxi-
mately equal to IPD2/IPD1 at IF = 10 mA.
2. BEST FIT DC NONLINEARITY (NLBF) is the maximum deviation expressed as a percentage of the full scale output of a “best t” straight line from
a graph of IPD2 vs. IPD1 with eleven equally distrib uted data points from 5 nA to 50 μA. IPD2 error to best t line is the deviation below and above
the best t line, expressed as a percentage of the full scale output.
3. ENDS FIT DC NONLINEARITY (NLEF) is the maximum deviation expressed as a percentage of full scale output of a straight line from the 5 nA to
the 50 μA data point on the graph of IPD2 vs. IPD1.
4. Device considered a two-terminal device: Pins 1, 2, 3, and 4 shorted together and pins 5, 6, 7, and 8 shorted together.
5. In accordance with UL 1577, each optocoupler is proof tested by applying an insulation test voltage of ≥6000 V rms for ≥1 second (leakage
detection current limit, II-O of 5 μA max.). This test is performed before the 100% production test for partial discharge (method b) shown in the
IEC/EN/DIN EN 60747-5-2 Insulation Characteris-tics Table (for Option #050 only).
6. Speci c performance will depend on circuit topology and components.
7. IMRR is de ned as the ratio of the signal gain (with signal applied to VIN of Figure 16) to the isolation mode gain (with VIN connected to input
common and the signal applied between the input and output commons) at 60 Hz, expressed in dB.
Package Characteristics
T
A = 25°C unless otherwise speci ed.
Test
Parameter Symbol Device Min. Typ. Max. Units Conditions Fig. Note
Input-Output VISO 5000 V rms RH ≤50%, 4, 5
Momentary-Withstand t = 1 min.
Voltage*
Resistance RI-O 1012 1013 Ω V
O = 500 VDC 4
(Input-Output)
1011 T
A = 100°C, 4
V
IO = 500 VDC
Capacitance CI-O 0.4 0.6 pF f = 1 MHz 4
(Input-Output)
*The Input-Output Momentary Withstand Voltage is a dielectric voltage rating that should not be interpreted as an input-output continuous
voltage rating. For the continuous voltage rating refer to the VDE 0884 Insulation Characteristics Table (if applicable), your equipment level safety
speci cation, or Application Note 1074, “Optocoupler Input-Output Endurance Voltage.”
10
Figure 5. NLBF vs. temperature.
Figure 2. Normalized K3 vs. input IPD. Figure 3. K3 drift vs. temperature. Figure 4. IPD2 error vs. input IPD (see note 4).
Figure 6. NLBF drift vs. temperature. Figure 7. Input photodiode CTR vs. LED input
current.
Figure 8. Typical photodiode leakage vs.
temperature.
Figure 9. LED input current vs. forward voltage. Figure 10. LED forward voltage vs. temperature.
I
LK
– PHOTODIODE LEAKAGE – nA
10.0
4.0
0.0
T
A
– TEMPERATURE – °C
6.0
2.0
8.0
-25-55 5 35 65 95 125
V
PD
= 15 V
DELTA K3 – DRIFT OF K3 TRANSFER GAIN
0.02
-0.005
-0.02
T
A
– TEMPERATURE – °C
0.01
0.005
-0.01
-0.015 = DELTA K3 MEAN
= DELTA K3 MEAN ± 2 • STD DEV
0.0
0.015
-25-55 5 35 65 95 125
0 V < V
PD
< 15 V
DELTA NL
BF
– DRIFT OF BEST-FIT NL – % PTS
0.02
-0.005
-0.02
T
A
– TEMPERATURE – °C
0.01
0.005
-0.01
-0.015 = DELTA NL
BF
MEAN
= DELTA NL
BF
MEAN ± 2 • STD DEV
0.0
0.015
-25-55 5 35 65 95 125
0 V < V
PD
< 15 V
5 nA < I
PD
< 50 µA
NORMALIZED K1 – INPUT PHOTODIODE CTR
0.0
0.5
0.2
IF – LED INPUT CURRENT – mA
2.0 6.0 12.0
0.6
0.4
0.3
4.0 8.0 10.0
0.7
0.8
0.9
1.0
1.1
1.2
14.0 16.0
-55°C
25°C
-40°C
85°C
100°C
NORMALIZED TO K1 CTR
AT IF = 10 mA, TA = 25°C
0 V < VPD1 < 15 V
VF – LED FORWARD VOLTAGE – V
1.5
1.2
TA – TEMPERATURE – °C
1.8
1.7
1.4
1.3
1.6
-25-55 5 35 65 95 125
IF = 10 mA
NORMALIZED K3 – TRANSFER GAIN
0.0
1.06
1.00
0.94
I
PD1
– INPUT PHOTODIODE CURRENT – µA
10.0 30.0 60.0
1.04
1.02
0.98
0.96
20.0 40.0 50.0
= NORM K3 MEAN
= NORM K3 MEAN ± 2 • STD DEV
NORMALIZED TO BEST-FIT K3 AT T
A
= 25°C,
0 V < V
PD
< 15 V
0.0
0.03
0.00
-0.03
I
PD1
– INPUT PHOTODIODE CURRENT – µA
10.0 30.0 60.0
0.02
0.01
-0.01
-0.02
20.0 40.0 50.0
= ERROR MEAN
= ERROR MEAN ± 2 • STD DEV
I
PD2
ERROR FROM BEST-FIT LINE (% OF FS)
T
A
= 25 °C, 0 V < V
PD
< 15 V
NLBF – BEST-FIT NON-LINEARITY – %
0.015
0.00
TA – TEMPERATURE – °C
0.03
0.025
0.01
0.005
= NLBF 50TH PERCENTILE
= NLBF 90TH PERCENTILE
0.02
0.035
-25-55 5 35 65 95 125
0 V < VPD < 15 V
5 nA < IPD < 50 µA
1.20
100
0.1
0.0001
VF – FORWARD VOLTAGE – VOLTS
1.30 1.50
10
1
0.01
0.001
1.40 1.60
IF – FORWARD CURRENT – mA
TA = 25°C
11
Figure 12. Basic isolation ampli er.
Figure 11. Thermal derating curve dependence of safety limiting value
with case temperature per IEC/EN/DIN EN 60747-5-2.
Figure 13. Unipolar circuit topologies.
0
800
300
0
TS – CASE TEMPERATURE – °C
25 75 150
600
500
200
100
50 100 125
PS OUTPUT POWER – mV
IS INPUT CURRENT – mA
400
700
900
1000
175
-
+
VIN
-
+
VOUT
VIN
-
+
-
+
VOUT
A) POSITIVE INPUT
VCC
B) POSITIVE OUTPUT
C) NEGATIVE INPUT D) NEGATIVE OUTPUT
IF
LED
IPD1 PD1
R1
VIN
A1
+
-
IPD2 PD2
R2
A2
-
+
VOUT
PD1
R1
VIN
A1
-
+
PD2 PD2
R2
A2
-
+
VOUT
A) BASIC TOPOLOGY
B) PRACTICAL CIRCUIT
C1
R3
VCC
LED
C2
12
Figure 15. Loop-powered 4-20 mA current loop circuits.
Figure 14. Bipolar circuit topologies.
-
+
V
OUT
+I
IN
-
+
-
+
+I
OUT
A) RECEIVER
B) TRANSMITTER
PD2
V
IN
-
+
V
CC
-I
IN
R1
R3
PD1
LED
D1
R2
R1
PD1
LED
-I
OUT
R2
R3
PD2
D1 Q1
-
+
-
+
VOUT
VIN
-
+
-
+
VOUT
A) SINGLE OPTOCOUPLER
VCC1
B) DUAL OPTOCOUPLER
VCC1
IOS1
VCC2
IOS2
VIN
-
+
VCC
13
Figure 18. Bipolar isolation ampli er.
Figure 16. High-speed low-cost analog isolator.
Figure 17. Precision analog isolation ampli er.
-
+
VMAG
-
+
VIN
OC1
PD1
+
-
OC2
PD1
R1
50 K
D2
C2 10 pf
C1 10 pf
D1 R4
680
R5
680
OC1
LED
OC2
LED
R3
180 K
R2
180 K
BALANCE
C3 10 pf
OC1
PD2
R6
180 K
R7
50 K
GAIN
OC2
PD2
VCC1 = +15 V
VEE1 = -15 V
VIN
VCC1 +5 V
R1
68 K
PD1
LED
R3
10 K
Q1
2N3906
R4
10
Q2
2N3904
VCC2 +5 V
R2
68 K
PD2
R5
10 K
Q3
2N3906
R6
10
Q4
2N3904
R7
470
VOUT
-
+
PD1
2
3A1
7
4
R1
200 K
INPUT
BNC 1%
C3
0.1µ
VCC1 +15 V
C1
47 P
LT1097
R6
6.8 K
R4
2.2 K
R5
270
Q1
2N3906
VEE1 -15 V
C4
0.1µ
R3
33 K
LED D1
1N4150
-
+
PD2
2
3
A2
7
4
C2
33 POUTPUT
BNC
174 K
LT1097
50 K
1 %
VEE2 -15 V
C6
0.1µ
R2
C5
0.1µ
VCC2 +15 V
6
6
14
Figure 20. SPICE model listing.
Figure 19. Magnitude/sign isolation ampli er.
-
+
VMAG
-
+
VIN OC1
PD1
+
-
D4
C2 10 pf
C1 10 pf
D3
R4
680
OC1
LED
R1
220 K
C3 10 pf
OC1
PD2
R5
180 K
R6
50 K
GAIN
R2
10 K
R3
4.7 K
D1
-
+
D2
+
-R7
6.8 K
VCC
R8
2.2 K
VSIGN
OC2
6N139
VCC1 = +15 V
VEE1 = -15 V
15
Figure 21. 4 to 20 mA HCNR200 receiver circuit.
Figure 22. 4 to 20 mA HCNR200 transmitter circuit.
-
+VOUT
-
+
VCC
5.5 V
R1
10 kΩ
+ILOOP
HCNR200
PD1
-ILOOP
R2
10 kΩ
R4
100 Ω
2N3906
Z1
5.1 V
0.1 µF
R3
25 Ω
0.001 µF
R5
80 kΩ
LM158
HCNR200
PD2
0.001 µF
2
HCNR200
LED
LM158
Design Equations:
VOUT / ILOOP = K3 (R5 R3) / R1 + R3)
K3 = K2 / K1 = Constant = 1
Note:
The two OP-AMPS shown are two separate LM158, and not two channels in a single dual package,
otherwise the loop side and output side will not be properly isolated.
Design Equations:
(ILOOP/Vin)=K3(R5+R3)/(R5R1)
K3 = K2/K1 = Constant ≈ 1
Note:
The two OP-AMPS shown are two separate LM158 IC’s, and NOT dual channels in a
single package, otherwise, the LOOP side and input side will not be properly isolated;
The 5V1 Zener should be properly selected to ensure that it conducts at 187μA;
-
+
80k Ω
PD1/IC1 LM158
IC2
LED/IC1
HCNR200
1nF
150 Ω
Q1
2N3906
R1
R2
Vcc
5.5V
Vin
0.8V~4V
C1
-
+
LM158
IC3
PD2/IC1
1nF
10k Ω
25 Ω
10k Ω
3k2Ω
5V1
100nF
100kΩ
150 Ω
Q2
Q3
Q4
2N3904
2N3904
2N3904
R3
R4
R5
R6
R7
R8
C2
C3
+I LOOP
-ILOOP
12V~40V
4 ~ 20mA
4mA (Vin=0.8V)
20mA(Vin=4V)
“0” @ 2200Hz
“1” @ 1200Hz
16
Theory of Operation
Figure 1 illustrates how the HCNR200/201 high-linearity
opto coup ler is con gured. The basic optocoupler con-
sists of an LED and two photodiodes. The LED and one of
the photodiodes (PD1) is on the input leadframe and the
other photodiode (PD2) is on the output leadframe. The
package of the optocoupler is constructed so that each
photo diode receives approxi mately the same amount of
light from the LED.
An external feedback ampli er can be used with PD1 to
monitor the light output of the LED and automatically
adjust the LED current to compensate for any non-linear-
ities or changes in light output of the LED. The feedback
ampli er acts to stabilize and linearize the light output
of the LED. The output photodiode then converts the
stable, linear light output of the LED into a current, which
can then be converted back into a voltage by another
ampli er.
Figure 12a illustrates the basic circuit topology for
implement ing a simple isolation ampli er using the
HCNR200/201 optocoupler. Besides the optocoupler,
two external op-amps and two resistors are required.
This simple circuit is actually a bit too simple to function
properly in an actual circuit, but it is quite useful for ex-
plaining how the basic isolation ampli er circuit works (a
few more components and a circuit change are required
to make a practical circuit, like the one shown in Figure
12b).
The operation of the basic circuit may not be immedi-
ately obvious just from inspecting Figure 12a, particu-
larly the input part of the circuit. Stated brie y, ampli er
A1 adjusts the LED current (IF), and therefore the current
in PD1 (IPD1), to maintain its “+” input terminal at 0 V. For
example, increasing the input voltage would tend to in-
crease the voltage of the “+” input terminal of A1 above
0 V. A1 ampli es that increase, causing IF to increase, as
well as IPD1. Because of the way that PD1 is connected,
IPD1 will pull the “+” terminal of the op-amp back toward
ground. A1 will continue to increase IF until its “+” termi-
nal is back at 0 V. Assuming that A1 is a perfect op-amp,
no current ows into the inputs of A1; therefore, all of the
current owing through R1 will ow through PD1. Since
the “+” input of A1 is at 0 V, the current through R1, and
there fore IPD1 as well, is equal to VIN/R1.
Essentially, ampli er A1 adjusts IF so that
I
PD1 = VIN/R1.
Notice that IPD1 depends ONLY on the input voltage and
the value of R1 and is independent of the light output
characteris tics of the LED. As the light output of the
LED changes with temperature, ampli er A1 adjusts IF
to compensate and maintain a constant current in PD1.
Also notice that IPD1 is exactly proportional to VIN, giving
a very linear relationship between the input voltage and
the photodiode current.
The relationship between the input optical power and
the output current of a photodiode is very linear. There-
fore, by stabiliz ing and linearizing IPD1, the light output of
the LED is also stabilized and linearized. And since light
from the LED falls on both of the photodiodes, IPD2 will be
stabilized as well.
The physical construction of the package determines the
relative amounts of light that fall on the two photodiodes
and, therefore, the ratio of the photodiode currents. This
results in very stable operation over time and tempera-
ture. The photodiode current ratio can be expressed as a
constant, K, where
K = IPD2/IPD1.
Ampli er A2 and resistor R2 form a trans-resistance am-
pli er that converts IPD2 back into a voltage, V
OUT, where
V
OUT = IPD2*R2.
Combining the above three equations yields an overall
expression relating the output voltage to the input volt-
age,
V
OUT/VIN = K*(R2/R1).
Therefore the relationship between VIN and V
OUT is con-
stant, linear, and independent of the light output
characteris tics of the LED. The gain of the basic isola tion
ampli er circuit can be adjusted simply by adjusting the
ratio of R2 to R1. The parameter K (called K3 in the electri-
cal speci cations) can be thought of as the gain of the
optocoupler and is speci ed in the data sheet.
Remember, the circuit in Figure 12a is simpli ed in order
to explain the basic circuit opera tion. A practical circuit,
more like Figure 12b, will require a few additional compo-
nents to stabilize the input part of the circuit, to limit the
LED current, or to optimize circuit performance. Example
applica tion circuits will be discussed later in the data
sheet.
17
to worry about. How ever, the second circuit requires two
optocouplers, separate gain adjustments for the posi-
tive and negative portions of the signal, and can exhibit
crossover distor tion near zero volts. The correct circuit to
choose for an applica tion would depend on the require-
ments of that particular application. As with the basic
isolation ampli er circuit in Figure 12a, the circuits in Fig-
ure 14 are simpli ed and would require a few additional
compo nents to function properly. Two example circuits
that operate with bipolar input signals are discussed in
the next section.
As a nal example of circuit design exibility, the simpli-
ed schematics in Figure 15 illus trate how to implement
4-20 mA analog current-loop transmitter and receiver
circuits using the HCNR200/201 optocoupler. An impor-
tant feature of these circuits is that the loop side of the
circuit is powered entirely by the loop current, eliminat-
ing the need for an isolated power supply.
The input and output circuits in Figure 15a are the same
as the negative input and positive output circuits shown
in Figures 13c and 13b, except for the addition of R3 and
zener diode D1 on the input side of the circuit. D1 regu-
lates the supply voltage for the input ampli er, while R3
forms a current divider with R1 to scale the loop current
down from 20 mA to an appropriate level for the input
circuit (<50 μA).
As in the simpler circuits, the input ampli er adjusts the
LED current so that both of its input terminals are at the
same voltage. The loop current is then divided
between R1 and R3. IPD1 is equal to the current in R1 and
is given by the following equation:
I
PD1 = ILOOP*R3/(R1+R3).
Combining the above equation with the equations used
for Figure 12a yields an overall expression relating the
output voltage to the loop current,
V
OUT/ILOOP = K*(R2*R3)/(R1+R3).
Again, you can see that the relationship is constant, lin-
ear, and independent of the charac teristics of the LED.
The 4-20 mA transmitter circuit in Figure 15b is a little dif-
ferent from the previous circuits, partic ularly the output
circuit. The output circuit does not directly generate an
output voltage which is sensed by R2, it instead uses Q1
to generate an output current which ows through R3.
This output current generates a voltage across R3, which
is then sensed by R2. An analysis similar to the one above
yields the following expression relating output current
to input voltage:
I
LOOP/VIN = K*(R2+R3)/(R1*R3).
Circuit Design Flexibility
Circuit design with the HCNR200/201 is very exible
because the LED and both photodiodes are acces sible
to the designer. This allows the designer to make perf-
ormance trade-o s that would otherwise be di cult to
make with commercially avail able isolation ampli ers
(e.g., band width vs. accuracy vs. cost). Analog isola tion
circuits can be designed for applications that have either
unipolar (e.g., 0-10 V) or bipolar (e.g., ±10 V) signals, with
positive or negative input or output voltages. Several
simpli ed circuit topologies illustrating the design ex-
ibility of the HCNR200/201 are discussed below.
The circuit in Figure 12a is con gured to be non-invert-
ing with positive input and output voltages. By simply
changing the polarity of one or both of the photodiodes,
the LED, or the op-amp inputs, it is possible to imple ment
other circuit con gu ra tions as well. Figure 13 illustrates
how to change the basic circuit to accommodate both
positive and negative input and output voltages. The in-
put and output circuits can be matched to achieve any
combina tion of positive and negative voltages, allowing
for both inverting and non-inverting circuits.
All of the con gurations described above are unipolar
(single polar ity); the circuits cannot accom mo date a sig-
nal that might swing both positive and negative. It is pos-
sible, however, to use the HCNR200/201 optocoupler to
implement a bipolar isolation ampli er. Two topologies
that allow for bipolar operation are shown in Figure 14.
The circuit in Figure 14a uses two current sources to
o set the signal so that it appears to be unipolar to the
optocoupler. Current source IOS1 provides enough o set
to ensure that IPD1 is always positive. The second current
source, IOS2, provides an o set of opposite polarity to ob-
tain a net circuit o set of zero. Current sources IOS1 and
IOS2 can be implemented simply as resistors connected to
suitable voltage sources.
The circuit in Figure 14b uses two optocouplers to obtain
bipolar operation. The rst optocoupler handles the pos-
itive voltage excursions, while the second optocoupler
handles the negative ones. The output photo diodes are
connected in an antiparallel con guration so that they
produce output signals of opposite polarity.
The rst circuit has the obvious advantage of requiring
only one optocoupler; however, the o set performance
of the circuit is dependent on the matching of IOS1 and
IOS2 and is also dependent on the gain of the optocoupler.
Changes in the gain of the opto coupler will directly af-
fect the o set of the circuit.
The o set performance of the second circuit, on the
other hand, is much more stable; it is inde pendent of
optocoupler gain and has no matched current sources
18
The preceding circuits were pre sented to illustrate the
exibility in designing analog isolation circuits using the
HCNR200/201. The next section presents several com-
plete schematics to illustrate practical applications of the
HCNR200/201.
Example Application Circuits
The circuit shown in Figure 16 is a high-speed low-cost
circuit designed for use in the feedback path of switch-
mode power supplies. This application requires good
bandwidth, low cost and stable gain, but does not re-
quire very high accuracy. This circuit is a good example
of how a designer can trade o accuracy to achieve
improve ments in bandwidth and cost. The circuit has a
bandwidth of about 1.5 MHz with stable gain character-
istics and requires few external components.
Although it may not appear so at rst glance, the circuit
in Figure 16 is essentially the same as the circuit in Fig-
ure 12a. Ampli er A1 is comprised of Q1, Q2, R3 and R4,
while ampli er A2 is comprised of Q3, Q4, R5, R6 and R7.
The circuit operates in the same manner as well; the only
di erence is the performance of ampli ers A1 and A2.
The lower gains, higher input currents and higher o set
voltages a ect the accuracy of the circuit, but not the
way it operates. Because the basic circuit operation has
not changed, the circuit still has good gain stability. The
use of discrete transistors instead of op-amps allowed
the design to trade o accuracy to achieve good band-
width and gain stability at low cost.
To get into a little more detail about the circuit, R1 is se-
lected to achieve an LED current of about 7-10 mA at the
nominal input operating voltage according to the fol-
lowing equation:
I
F = (VIN/R1)/K1,
where K1 (i.e., IPD1/IF) of the optocoupler is typically about
0.5%. R2 is then selected to achieve the desired output
volt age according to the equation,
V
OUT/VIN = R2/R1.
The purpose of R4 and R6 is to improve the dynamic re-
sponse (i.e., stability) of the input and output circuits by
lowering the local loop gains. R3 and R5 are selected to
provide enough current to drive the bases of Q2 and Q4.
And R7 is selected so that Q4 operates at about the same
collector current as Q2.
The next circuit, shown in Figure 17, is designed to achieve
the highest possible accuracy at a reasonable cost. The
high accuracy and wide dynamic range of the circuit is
achieved by using low-cost precision op-amps with very
low input bias currents and o set voltages and is limited
by the performance of the opto coupler. The circuit is de-
signed to operate with input and output voltages from
1 mV to 10 V.
The circuit operates in the same way as the others. The
only major di erences are the two compensa tion capaci-
tors and additional LED drive circuitry. In the high-speed
circuit discussed above, the input and output circuits are
stabilized by reducing the local loop gains of the input
and output circuits. Because reducing the loop gains
would decrease the accuracy of the circuit, two compen-
sation capacitors, C1 and C2, are instead used to improve
circuit stability. These capacitors also limit the bandwidth
of the circuit to about 10 kHz and can be used to reduce
the output noise of the circuit by reducing its bandwidth
even further.
The additional LED drive circuitry (Q1 and R3 through
R6) helps to maintain the accuracy and band width of the
circuit over the entire range of input voltages. Without
these components, the transcon duc t ance of the LED
driver would decrease at low input voltages and LED
currents. This would reduce the loop gain of the input
circuit, reducing circuit accuracy and bandwidth. D1 pre-
vents excessive reverse voltage from being applied to
the LED when the LED turns o completely.
No o set adjustment of the circuit is necessary; the gain
can be adjusted to unity by simply adjusting the 50 kohm
poten tiometer that is part of R2. Any OP-97 type of op-
amp can be used in the circuit, such as the LT1097 from
Linear Technology or the AD705 from Analog Devices,
both of which o er pA bias currents, μV o set voltages
and are low cost. The input terminals of the op-amps and
the photodiodes are connected in the circuit using Kelvin
connections to help ensure the accuracy of the circuit.
The next two circuits illustrate how the HCNR200/201 can
be used with bipolar input signals. The isolation ampli er
in Figure 18 is a practical implemen tation of the circuit
shown in Figure 14b. It uses two opto couplers, OC1 and
OC2; OC1 handles the positive portions of the input sig-
nal and OC2 handles the negative portions.
Diodes D1 and D2 help reduce crossover distortion by
keeping both ampli ers active during both positive and
negative portions of the input signal. For example, when
the input signal positive, optocoupler OC1 is active while
OC2 is turned o . However, the ampli er control ling OC2
is kept active by D2, allowing it to turn on OC2 more rap-
idly when the input signal goes negative, thereby reduc-
ing crossover distortion.
Balance control R1 adjusts the relative gain for the posi-
tive and negative portions of the input signal, gain con-
trol R7 adjusts the overall gain of the isolation ampli er,
and capac i tors C1-C3 provide compensa tion to stabilize
the ampli ers.
For product information and a complete list of distributors, please go to our website: www.avagotech.com
Avago, Avago Technologies, and the A logo are trademarks of Avago Technologies in the United States and other countries.
Data subject to change. Copyright © 2005-2011 Avago Technologies. All rights reserved. Obsoletes AV01-0567EN
AV02-0886EN - December 10, 2011
The nal circuit shown in Figure 19 isolates a bipolar
analog signal using only one optocoupler and generates
two output signals: an analog signal proportional to the
magnitude of the input signal and a digital signal cor-
responding to the sign of the input signal. This circuit is
especially useful for applica tions where the output of
the circuit is going to be applied to an analog-to-digital
converter. The primary advantages of this circuit are very
good linearity and o set, with only a single gain adjust-
ment and no o set or balance adjustments.
To achieve very high linearity for bipolar signals, the
gain should be exactly the same for both positive and
negative input polarities. This circuit achieves excellent
linearity by using a single optocoupler and a single input
resistor, which guarantees identical gain for both posi-
tive and negative polarities of the input signal. This pre-
cise matching of gain for both polari ties is much more
di cult to obtain when separate components are used
for the di erent input polari ties, such as is the pre vious
circuit.
The circuit in Figure 19 is actually very similar to the pre-
vious circuit. As mentioned above, only one optocoupler
is used. Because a photodiode can conduct current in
only one direction, two diodes (D1 and D2) are used to
steer the input current to the appropriate terminal of
input photodiode PD1 to allow bipolar input currents.
Normally the forward voltage drops of the diodes would
cause a serious linearity or accuracy problem. However,
an additional ampli er is used to provide an appropriate
o set voltage to the other ampli ers that exactly cancels
the diode voltage drops to maintain circuit accuracy.
Diodes D3 and D4 perform two di erent functions; the
diodes keep their respective ampli ers active indepen-
dent of the input signal polarity (as in the previous cir-
cuit), and they also provide the feedback signal to PD1
that cancels the voltage drops of diodes D1 and D2.
Either a comparator or an extra op-amp can be used to
sense the polarity of the input signal and drive an inex-
pensive digital optocoupler, like a 6N139.
It is also possible to convert this circuit into a fully bipolar
circuit (with a bipolar output signal) by using the output
of the 6N139 to drive some CMOS switches to switch the
polarity of PD2 depending on the polarity of the input
signal, obtaining a bipolar output voltage swing.
HCNR200/201 SPICE Model
Figure 20 is the net list of a SPICE macro-model for the
HCNR200/201 high-linearity optocoupler. The macro-
model accurately re ects the primary characteristics of
the HCNR200/201 and should facilitate the design and
understanding of circuits using the HCNR200/201 opto-
coupler.
