General Description
The MAX16812 is a peak-current-mode LED driver with
an integrated 0.2Ω power MOSFET designed to control
the current in a single string of high-brightness LEDs
(HB LEDs). The MAX16812 can be used in multiple
converter topologies such as buck, boost, or buck-boost.
The MAX16812 operates over a 5.5V to 76V wide supply
voltage range.
The MAX16812 features a low-frequency, wide-range
brightness adjustment (100:1), analog and PWM dim-
ming control input, as well as a resistor-programmable
EMI suppression circuitry to control the rise and fall times
of the internal switching MOSFET. A high-side LED cur-
rent-sense amplifier and a dimming MOSFET driver are
also included, simplifying the design and reducing the
total component count.
The MAX16812 uses peak-current-mode control, adjust-
able slope compensation that allows for additional design
flexibility. The device has two current regulation loops.
The first loop controls the internal switching MOSFET
peak current, while the second current regulation loop
controls the LED current. Switching frequency can be
adjusted from 125kHz to 500kHz.
Additional features include adjustable UVLO, soft-start,
external enable/disable input, thermal shutdown, a 1.238V
1% accurate buffered reference, and an on-chip oscillator.
An internal 5.2V linear regulator supplies up to 20mA to
power external devices.
The MAX16812 is available in a thermally enhanced 5mm
x 5mm, 28-pin TQFN-EP package and is specified over
the automotive -40°C to +125°C temperature range.
Applications
●Architectural and Industrial Lighting
Features
●Integrated 76V, 0.2Ω (typ) Power MOSFET
●5.5V to 76V Wide Input Range
●Adjustable LED Current with 5% Accuracy
●Floating Differential LED Current-Sense Amplifier
●Floating Dimming N-Channel MOSFET Driver
●PWM LED Dimming with:
• PWM Control Signal
• Analog Control Signal
• Chopped VIN Input
●Peak-Current-Mode Control
●125kHz to 500kHz Adjustable Switching Frequency
●Adjustable UVLO and Soft-Start
●Output Overvoltage Protection
●5µs LED Current Rise/Fall Times During Dimming
Minimize EMI
●Overtemperature and Short-Circuit Protection
19-0880; Rev 1; 4/14
Typical Application Circuit and Pin Configuration appear
at end of data sheet.
+Denotes a lead(Pb)-free/RoHS-compliant package.
*EP = Exposed pad.
PART TEMP RANGE PIN-PACKAGE
MAX16812ATI+ -40°C to +125°C 28 TQFN-EP*
VIN
CIN
RTGRM
CH_REG
ROV1
ROV2
CTGRM
RT
DIM
TGRM
VOUT
L_REG
RT
EN
IN
LV
RCS
DOUT
VOUT
SRC
GT
DRV
SLP
COMP
RCOMP1
BUCK-BOOST CONFIGURATION
CCOMP1
CSLP
RSRC
COUT
RCOMP2
CS-
CS+
DGT
DD
H_REG
HV
LX
OV
SGND
AGND
REFI
REF
CS_OUT
FB
MAX16812
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Simplied Diagram
Ordering Information
EVALUATION KIT AVAILABLE
(All voltages are referenced to AGND, unless otherwise noted.)
SGND ...................................................................-0.3V to +0.3V
IN, EN, LX, DIM ..................................................... -0.3V to +80V
L_REG, GT, DRV ....................................................-0.3V to +6V
RT, REF, REFI, CS_OUT, FB, COMP, SRC,
SLP, TGRM, OV ..................................................-0.3V to +6V
LV, HV, CS-, CS+, DGT, DD, H_REG ..................-0.3V to +80V
CS+, DGT, H_REG to LV ......................................-0.3V to +12V
CS- to LV ..............................................................-0.3V to +0.3V
CS+ to CS- ............................................................-0.3V to +12V
DD to LV ...................................................................-1V to +80V
Maximum Current into Any Pin (except LX, SRC) ........... ±20mA
Maximum Current into LX and SRC ......................................+2A
Continuous Power Dissipation (TA = +70°C)
28-Pin TQFN 5mm x 5mm
(derate 34.65mW/°C* above +70°C) .........................2759mW
Operating Temperature Range ......................... -40°C to +125°C
Junction Temperature ...................................................... +150°C
Storage Temperature Range ............................ -65°C to +150°C
Lead Temperature (soldering, 10s) .................................+300°C
(VIN = VEN = 12V, CL_REG = 3.3µF, CH_REG = 1µF, CREF = 47nF, VTGRM = 0V, RSRC = 0.2Ω, TA = TJ = -40°C to +125°C, unless
otherwise noted. Typical values are at TA = +25°C.)
PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS
Input Voltage Range VIN 5.5 76.0 V
Quiescent Supply IQVTGRM = 1V, VDIM = 0V 0.3 2.5 mA
Shutdown Supply Current ISHDN VEN ≤ 300mV 20 45 µA
Internal MOSFET On-Resistance RDSON ILX = 1A, VIN > 10V, VGT = VDRV = 5V 0.2 0.4 Ω
Output Current Accuracy ILED ILED = 350mA, RCS = 1Ω -5 +5 %
Peak Switch Current Limit ILXLIM 2.6 3.1 3.6 A
Hiccup Switch Current 6 A
Switch Leakage Current ILXLEAK VEN = 0V, VLX = 76V, VGT = 0V 1 10 µA
UNDERVOLTAGE LOCKOUT
IN Undervoltage Lockout UVLO VIN rising 4.6 4.9 5.3 V
UVLO Hysteresis 100 mV
EN Threshold Voltage VEN_THUP VEN rising 1.2 1.38 1.6 V
EN Hysteresis 100 mV
REFERENCE (REF) AND LOW-SIDE LINEAR REGULATOR (L_REG)
Startup Response Time tPOR VIN or VEN rising 50 µs
Reference Voltage VREF IREF = 10µA 1.190 1.238 1.288 V
Reference Soft-Start Charging
Current IREF_SLEW VREF = 0V 25 40 60 µA
L_REG Supply Voltage VIN = 7.5V, IL_REG = 1mA 4.9 5.2 5.5 V
L_REG Load Regulation IL_REG = 20mA 20 Ω
L_REG Dropout Voltage IL_REG = 25mA 400 mV
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MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Electrical Characteristics
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these
or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect
device reliability.
*As per JEDEC51 standard (multilayer board).
Absolute Maximum Ratings
(VIN = VEN = 12V, CL_REG = 3.3µF, CH_REG = 1µF, CREF = 47nF, VTGRM = 0V, RSRC = 0.2Ω, RCS = 1Ω, TA = TJ = -40°C to +125°C,
unless otherwise noted. Typical values are at TA = +25°C.)
(VIN = VEN = 12V, CL_REG = 3.3µF, CH_REG = 1µF, CREF = 47nF, VTGRM = 0V, RSRC = 0.2Ω, TA = TJ = -40°C to +125°C, unless
otherwise noted. Typical values are at TA = +25°C.)
PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS
HIGH-SIDE UNDERVOLTAGE LOCKOUT AND LINEAR REGULATOR (H_REG) ((VHV - VLV) = 21V)
H_REG Input-Voltage Threshold VH_REG is rising 3.60 3.887 4.20 V
H_REG Supply Voltage IH_REG = 0 4.75 5 5.40 V
H_REG Load Regulation IH_REG = 0 to 3mA 80 Ω
Dropout Voltage IH_REG = 5mA 820 mV
HIGH-SIDE CURRENT-SENSE AMPLIFIERS (VHV - VLV) = 21V
CS- Input Bias Current ICS- VCS- = VLV, (VCS+ - VCS-) = -0.1V 500 µA
CS+ Input Bias Current ICS+ VCS- = VLV, (VCS+ - VCS-) = 0.1V -1 +1 µA
Input Voltage Range VCS- = VLV 0 0.25 V
Minimum Output Current ICS_OUT
Sinking 25 µA
Sourcing 400
Output Voltage Range VCS_OUT 0 1.5 V
DC Voltage Gain 4 V/V
Unity-Gain Bandwidth 0.8 MHz
Maximum REFI Input Voltage VREFI 1.0 V
PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS
PWM COMPARATOR
COMP Input Leakage Current ILKCOMP VCOMP = 1V, VSRC = 0.5V, VTGRM = 1V,
VDIM = 0.5V -0.10 +0.10 µA
SRC Input Leakage Current ILKSRC VCOMP = 0V, VSRC = 0.5V, VTGRM = 0V,
VDIM = 0.5V -5 +5 µA
Comparator Offset Voltage VOS(EA) (VCOMP - VSRC) = VOS 860 mV
Input Voltage Range VSRC VCOMP = VSRC + 860mV 0 1.23 V
Propagation Delay tPD 50mV overdrive 100 ns
ERROR AMPLIFIER
FB Input Current VFB = 1V, VREFI = 1.2V -100 +100 nA
REFI Input Current VFB = 1V, VREFI = 1V -100 +100 nA
Error-Amplifier Offset Voltage VOS VFB = VCOMP = 1.2V -23 +23 mV
Input Common-Mode Range VFB = (VCOMP - 0.9V) 0 1.5 V
Source Current ICOMP (VREFI - VFB) ≥ 0.5V 300 µA
Sink Current (VFB - VREFI) ≥ 0.5V 80 µA
COMP Clamp Voltage VCOMP VREF = 1.2V, VFB = 0V 1.20 2.56 V
DC Gain 72 dB
Unity-Gain Bandwidth 0.8 MHz
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MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Electrical Characteristics
Electrical Characteristics (continued)
(VIN = VEN = 12V, CL_REG = 3.3µF, CH_REG = 1µF, CREF = 47nF, VTGRM = 0V, RSRC = 0.2Ω, RCS = 1Ω, TA = TJ = -40°C to +125°C,
unless otherwise noted. Typical values are at TA = +25°C.)
PARAMETER SYMBOL CONDITIONS MIN TYP MAX UNITS
HIGH-SIDE DIMMING LINEAR REGULATOR ((VHV - VLV) = 21V)
Minimum Output Current IDGT
VLV = VCS-, (VCS+ - VCS-) = 0.3V,
(VDD - VLV) = 1V, VDIM = 1V, VTGRM = 0V,
VDGT = 1V, VREFI = 1.0V, sinking
1.2
mA
VLV = VCS-, (VCS+ - VCS-) = 0.2V,
(VDD - VLV) = 1V, VTGRM = 0V, VDGT = 3V,
VREFI = 1.0V, VDIM = 1V, sourcing
1.2
Output Voltage Range 0.2 5.0 V
DC Gain CDGT = 1nF to LV 60 dB
DD Input Bias Current IDD (VDD - VCS-) = 0.5V -3 +3 µA
DD Input Low Threshold VTGRM = 0V, VDIM = 1V, VREFI = 1.2V,
(VDGT - VLV) > 1.5V, VDD falling 0.25 0.50 0.75 V
DIMMING ((VHV - VLV) = 21V)
DIM Input Bias Current IDIM VDIM = 1.1V -1 +1 µA
TGRM Input High Threshold 1.18 1.23 1.27 V
TGRM Reset High-to-TGRM Low
Pulse Width 1 µs
TGRM Reset Switch RDS(ON) VTGRM = 1.3V 20 Ω
Dimming Rise and Fall LED
Current Times 5 µs
OVERVOLTAGE PROTECTION (OV)
OV Input High Threshold VOV rising 1.180 1.230 1.292 V
OV Input Threshold Hysteresis 14 mV
OV Input Bias Current IOV VOV = 1.1V -1 +1 µA
INTERNAL OSCILLATOR CLOCK
Internal Clock Frequency fOSC
RT = 2MΩ to AGND 470 525 570 kHz
RT = 50kΩ to AGND 105 125 155
SLOPE COMPENSATION INPUT (SLP)
SLP Input Current ISLP VSLP = 0V 150 µA
LOW-SIDE GATE DRIVE (DRV)
DRV Output Low Impedance RDRV_LO DRV sinking 20mA 3 30 Ω
DRV Output High Impedance RDRV_HI DRV sourcing 20mA 10 45 Ω
INTERNAL POWER MOSFET
GT Input Leakage Current VGT = 0 to 5V -1 +1 µA
Internal MOSFET Gate-to-
Source Threshold Voltage VTH 2.5 V
Internal MOSFET Gate Charge QgVLX = 50V 8 nC
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MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Electrical Characteristics (continued)
(VIN = VEN = 12V, CL_REG = 3.3µF, CH_REG = 1µF, VTGRM = 0V, TA = +25°C, unless otherwise noted.)
EN UVLO THRESHOLD
vs. TEMPERATURE
MAX16812 toc08
TEMPERATURE (°C)
EN UVLO (V)
1109580655035205-10-25
1.05
1.20
1.35
1.50
1.45
1.40
1.30
1.25
1.15
1.10
1.00
-40 125
VEN RISING
IN UVLO THRESHOLD
vs. TEMPERATURE
MAX16812 toc07
TEMPERATURE (°C)
IN UVLO (V)
1109580655035205-10-25
5.01
5.04
5.07
5.10
5.09
5.08
5.06
5.05
5.03
5.02
5.00
-40 125
VIN FALLING
IN UVLO THRESHOLD
vs. TEMPERATURE
MAX16812 toc06
TEMPERATURE (°C)
IN UVLO THRESHOLD (V)
1109580655035205-10-25
5.05
5.10
5.15
5.20
5.00
-40 125
VIN RISING
VREF vs. TEMPERATURE
MAX16812 toc05
TEMPERATURE (°C)
VREF (V)
1109580655035205-10-25
1.22
1.23
1.24
1.25
1.21
-40 125
IREF = 10µA
SHUTDOWN CURRENT
vs. TEMPERATURE
MAX16812 toc04
TEMPERATURE (°C)
SHUTDOWN CURRENT (µA)
1109580655035205-10-25
5
10
15
20
25
30
0
-40 125
SWITCH CURRENT LIMIT
vs. TEMPERATURE
MAX16812 toc03
TEMPERATURE (°C)
SWITCH CURRENT LIMIT (A)
11095-25 -10 5 35 50 6520 80
2.950
3.000
3.050
3.100
3.150
3.200
3.250
3.300
2.900
-40 125
RDS(ON) vs. VGT
MAX16812 toc02
VGT (V)
RDS(ON) (Ω)
6.45.84.6 5.23.4 4.02.8
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
1.8
2.0
0
2.2 7.0
TA = +25C
RDS(ON) vs. ILX
MAX16812 toc01
ILX (A)
RDS(ON) (Ω)
2.52.01.5
0.05
0.10
0.15
0.20
0.25
0.30
0.35
0.40
0.45
0
1.0 3.0
TA = +125C
TA = +25C
TA = -40C
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MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Typical Operating Characteristics
(VIN = VEN = 12V, CL_REG = 3.3µF, CH_REG = 1µF, VTGRM = 0V, TA = +25°C, unless otherwise noted.)
VH_REG vs. TEMPERATURE
MAX16812 toc15
TEMPERATURE (°C)
VH_REG (V)
1109580655035205-10-25
4.3
4.6
4.9
5.2
5.1
5.0
4.8
4.7
4.5
4.4
4.2
-40 125
(VHV - VLV) = 21V
ILOAD = 3mA
VH_REG vs. IH_REG
MAX16812 toc14
IH_REG (mA)
VH_REG (V)
2.52.01.51.00.5
4.55
4.60
4.65
4.70
4.75
4.80
4.85
4.90
4.95
5.00
4.50
0 3.0
(VHV - VLV) = 6V
VIN = 12V
VH_REG IS MEASURED
WITH RESPECT TO VLV
VH_REG THRESHOLD
vs. TEMPERATURE
MAX16812 toc13
TEMPERATURE (°C)
VH_REG THRESHOLD (V)
1109580655035205-10-25
3.6
3.9
4.2
4.1
4.0
3.8
3.7
3.5
3.4
-40 125
OSCILLATOR FREQUENCY vs. RT
MAX16812 toc12
RT (MΩ)
OSCILLATOR FREQUENCY (kHz)
10.1
100
200
300
400
500
600
0
0.01 10
OSCILLATOR FREQUENCY
vs. TEMPERATURE
MAX16812 toc11
TEMPERATURE (°C)
OSCILLATOR FREQUENCY (kHz)
1109580655035205-10-25
100
200
300
400
500
600
0
-40 125
RT = 2MΩ
RT = 180kΩ
RT = 50kΩ
VL_REG vs. IL_REG
MAX16812 toc10
IL_REG (mA)
VL_REG (V)
181612 144 6 8 102
4.6
4.7
4.8
4.9
5.0
5.1
5.2
5.3
5.4
5.5
4.5
0 20
TA = +125C
TA = +25C
TA = -40C
VIN = 7.5V
EN UVLO THRESHOLD
vs. TEMPERATURE
MAX16812 toc09
TEMPERATURE (°C)
EN UVLO (V)
1109580655035205-10-25
1.05
1.20
1.35
1.50
1.45
1.40
1.30
1.25
1.15
1.10
1.00
-40 125
VEN FALLING
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MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Typical Operating Characteristics (continued)
PIN NAME FUNCTION
1 FB Low-Side Error Amplifier’s Inverting Input
2 COMP Low-Side Error Amplifier’s Output. Connect a compensation network from COMP to FB for stable operation.
3 REFI Reference Input. VREFI provides the reference voltage for the high-side current-sense amplifier to set the
LED current.
4 REF +1.23V Reference Output. Connect an appropriate soft-start capacitor from REF to AGND.
5 CS_OUT High-Side Current-Sense Amplifier Output. VCS_OUT is proportional to the current through RCS.
6 AGND Analog Ground
7 EN
Enable Input/Undervoltage Lockout. Connect EN to IN through a resistive voltage-divider to program the
UVLO threshold. Connect EN directly to IN to set up the device for 5V internal threshold. Apply a logic-level
input to EN to enable/disable the device.
8 IN Positive Power-Supply Input. Bypass with a 1µF ceramic capacitor to AGND.
9 L_REG 5V Low-Side Regulator Output. Bypass with a 3.3µF ceramic capacitor to AGND.
10 SGND Signal Ground
11 DD MOSFET’s Drain Voltage-Sense Input. Connect DD to the drain of the external dimming MOSFET.
12 DGT External Dimming MOSFET’s Gate Drive
13 CS+ High-Side Current-Sense Amplifier’s Positive Input. Connect RCS between CS+ and CS-. CS+ is
referenced to LV.
14 CS- High-Side Current-Sense Amplifier’s Negative Input. Connect RCS between CS- and CS+. CS- is
referenced to LV.
15 LV High-Side Reference Voltage Input. A DC voltage at LV sets the lowest reference point for the high-side
current-sense and dimming MOSFET control circuitry.
16 H_REG High-Side Regulator Output. H_REG provides a regulated supply for high-side circuitry. Bypass with a 1µF
ceramic capacitor to LV.
17 HV High-Side Positive Supply Voltage Input. HV provides power for dimming and LED current-sense circuitry.
HV is referenced to LV.
18 DRV Internal MOSFET Gate Driver Output. Connect to a resistor between DRV and GT to set the rise and fall
times at LX.
19 GT Internal MOSFET GATE. Connect a resistor between GT and DRV to set the rise and fall times at LX.
20, 21 LX Internal MOSFET Drain
22, 23 SRC Internal Power MOSFET Source
24 SLP Slope Compensation Setting. Connect an appropriate external capacitor from SLP to AGND to generate a
ramp signal for stable operation.
25 TGRM Dimming Comparator’s Reference/Ramp Generator
26 DIM Dimming Control Input
27 RT Resistor-Programmable Internal Oscillator Setting. Connect a resistor from RT to AGND to set the internal
oscillator frequency.
28 OV
Overvoltage Protection Input. Connect OV to HI through a resistive voltage-divider to AGND to set the
overvoltage limit for the load. When the voltage at OV exceeds the 1.238V (typ) threshold, the gate drive
(DRV) for the switching MOSFET is disabled. Once VOV goes below 1.238V by 14mV, the switching
MOSFET turns on again.
— EP Exposed Pad. Connect EP to a large-area ground plane for effective power dissipation. Do not use as the
IC ground connection.
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MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Pin Description
Figure 1. Functional Diagram
LDOH
POR
3.88V 1.2X
1.1X
1X
PREG BG
VREF
LDOL
OSC
tD = 200ns
UVLO/
POR
DIM
RAMP
REF
CMP
CMP
IHI CSA
ADIM
DS
DRMP
0.5V
G1
LATCH
QS
R
1X
LOGIC
CONTROL
EN
ERROR
AMPLIFIER
AND
DIMMING
S/H
VREFI = 1.2V
VRAMP = 0.3V
CMP
OVP
CMP
1.238V
1.238V
2µs PULSE
LOW TO DISCHARGE
DIM
SIGNAL
2.5V
VDD
1.2V
SGND
HICCUP
0.6V
ILIM
PWM
VBE
X0.2
X1
MAX16812
HV
H_REG
LV
IN
L_REG
EN
REF
RT
DIM
TGRM
OV
SGND AGND
DD
CS+
CS-
LX
LX
SRC
SRC
GT
DRV
SLP
COMP
FB
CS_OUT
REFI
DGT
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8
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Detailed Description
The MAX16812 is a current-mode PWM LED driver with
an integrated 0.2Ω power MOSFET for use in driving HB
LEDs. By using two current regulation loops, 5% LED
current accuracy is achieved. One current regulation
loop controls the internal MOSFET peak current through
a sense resistor (RSRC) from SRC to ground, while the
other current regulation loop controls the average LED
current in a single LED string through another sense
resistor (RCS) in series with the LEDs.
The MAX16812 includes a cycle-by-cycle current limit
that turns off the gate drive to the internal MOSFET
during an overcurrent condition. The MAX16812 features
a programmable oscillator that simplifies and optimizes
the design of magnetics. The MAX16812 is well suited
for inputs from 5.5V to 76V. An external resistor in series
with the internal MOSFET gate can control the rise and
fall times on the drain of the internal switching MOSFET,
therefore minimizing EMI problems.
The MAX16812 high-frequency, current-mode PWM
HB LED driver integrates all the necessary building blocks
for driving a series LED string in an adjustable constant
current mode with PWM dimming. Current-mode control
with leading-edge blanking simplifies control-loop design,
and an external adjustable slope-compensation control
stabilizes the inner current-mode loop when operating at
duty cycles above 50%.
An input undervoltage lockout (UVLO) programs the input
supply startup voltage. An external voltage-divider on
EN programs the supply startup voltage. If EN is directly
connected to the input, the UVLO is set at 5V. A single
external resistor from RT to AGND programs the switch-
ing frequency from 125kHz to 500kHz.
Wide contrast (100:1) PWM dimming can be achieved
with the MAX16812. A DC input on DIM controls the
dimming duty cycle. The dimming frequency is set by
the sawtooth ramp frequency on TGRM (see the PWM
Dimming section). In addition, PWM dimming can be
achieved by applying a PWM signal to DIM with TGRM
set to a DC voltage less than 1.238V. A floating high-volt-
age driver drives an external n-channel MOSFET in series
with the LED string. REFI allows analog dimming of the
LED current, further increasing the effective dimming
range over PWM alone. The MAX16812 has a 5µs pre-
programmed LED current rise and fall time.
A nonlatching overvoltage protection limits the voltage on
the internal switching MOSFET under open-circuit condi-
tions in the LED string. The internal thermal shutdown cir-
cuit protects the device if the junction temperature should
exceed +165°C.
Current-Mode Control
The MAX16812 offers a current-mode control opera-
tion feature with leading-edge blanking that blanks the
sensed current signal applied to the input of the PWM
current-mode comparator. In addition, a current-limit com-
parator monitors the same signal at all times and provides
cycle-by-cycle current limit. An additional hiccup com-
parator limits the absolute peak current to two times the
cycle-by-cycle current limit. The leading-edge blanking of
the current-sense signal prevents noise at the PWM com-
parator input from prematurely terminating the on-cycle.
The switch current-sense signal contains a leading-edge
spike that results from the MOSFET gate-charge current,
and the capacitive and diode reverse-recovery current of
the power circuit. The MAX16812’s capacitor-adjustable
slope-compensation feature allows for easy stabilization
of the inner switching MOSFET current-mode loop. Upon
triggering the hiccup current limit, the soft-start capacitor
on REF is discharged and the gate drive to DRV is dis-
abled. Once the inductor current falls below the hiccup
current limit, the soft-start capacitor is released and it
begins to charge after 10µs.
Slope Compensation
The MAX16812 uses an internal ramp generator for
slope compensation. The internal ramp signal resets at
the beginning of each cycle and slews at the rate pro-
grammed by the external capacitor connected at SLP
and an internal ISLP current source of 150µA. An internal
attenuator attenuates the actual slope compensation
signal by a factor of 0.2. Adjust the MAX16812 slew-rate
capacitor by using the following equation:
SLP
SLOPE
C 0.2 SR
= ×
where ISLP is the charging current in mA and CSLOPE is
the slope compensation capacitance on the SLP in µF,
and SR is the designed slope in mV/µs.
When using the MAX16812 for internal switching MOSFET
duty cycles greater than 50%, the following conditions
must be met to avoid current-loop subharmonic oscilla-
tions.
SRC IND_OFF
0.5 R V
SR mV / s
L
××
≥µ
where RSRC is in mΩ, VIND_OFF is in volts, and L is in
µH. L is the inductor connected to the LX pin of the
internal switching MOSFET and VIND_OFF is the voltage
across the inductor during the off-time of the internal
MOSFET.
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│
9
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Undervoltage Lockout
The MAX16812 features an adjustable UVLO through the
enable input (EN). Connect EN directly to IN to use the 5V
default UVLO. Connect EN to IN through a resistive divid-
er to ground to set the UVLO threshold. The MAX16812
is enabled when VEN exceeds the 1.38V (typ) threshold.
Calculate the EN UVLO resistor-divider values as follows
(see Figure 2):
EN
UV1 UV2
UVLO EN
V
R R x
V - V

=


where RUV1 is in the 20kΩ range, VEN is the 1.38V
(typ) EN threshold voltage, and VUVLO is the desired
input-voltage UVLO threshold in volts. Due to the 100mV
hysteresis of the UVLO threshold, capacitor CEN is
required to prevent chattering at the UVLO threshold due
to line impedance drops at power-up and during dimming.
If the undervoltage setting is very close to the required
minimum operating voltage, there can be jumps in the
voltage at IN while dimming. CEN should be large enough
to limit the ripple on EN to less than 100mV (EN hystere-
sis) under these conditions so that it does not turn on and
off due to the ripple on IN.
Soft-Start
The soft-start feature of the MAX16812 allows the LED
string current to ramp up in a controlled manner, thus
minimizing output-voltage overshoot. While the part is in
UVLO, CREF is discharged (Figure 3). Upon coming out
of UVLO, an internal current source starts charging CREF
during the soft-start cycle. Use the following equation to
calculate total soft-start e:
ST REF REF
1.238
t C I
= ×
where IREF is 40µA, CREF is in µF, and tST is in seconds.
Operation begins when REF ramps above 0.6V. Once
the soft-start is complete, REF is regulated to 1.238V, the
internal voltage reference.
Low-Side Internal
Switching MOSFET Driver Supply (L_REG)
L_REG is the regulated (5.2V) internal supply voltage
capable of delivering 20mA. L_REG provides power to
the gate drive of the internal switching power MOSFET.
VL_REG is referenced to AGND. Connect a 3.3µF ceramic
capacitor from L_REG to AGND.
High-Side Regulator (H_REG)
H_REG is a low-dropout linear regulator referenced
to LV. H_REG provides the gate drive for the external
n-channel dimming MOSFET and also powers up the
MAX16812’s LED current-sense circuitry. Bypass H_REG
to LV with a 1µF ceramic capacitor.
Figure 3. Soft-Start SettingFigure 2. UVLO Threshold Setting
MAX16812
VIN
IN
AGND
REF
CREF
MAX16812
VIN
IN
AGND
EN
RUV2
RUV1
CEN
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10
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
High-Side Current-Sense Output (CS_OUT)
A high-side transconductance amplifier converts the volt-
age across the LED current-sense resistor (RCS) into
an internal current output. This current flows through an
internal resistor connected to AGND. The voltage gain for
the LED current-sense signal is 4. The amplified signal is
then buffered and connected through an internal switch
to CS_OUT.
Internal Error Amplier
The MAX16812 includes a built-in voltage-error amplifi-
er, which can be used to close the feedback loop. The
internal LED current-sense output signal is buffered
internally and then connected to CS_OUT through an
internal switch. CS_OUT is connected to the inverting
input (FB) pin of the error amplifier through a resistor.
See Figures 4 and 5. The reference voltage for the out-
put current is connected to REFI, the noninverting input
of the error amplifier. When the internal dimming signal
is low, COMP is disconnected from the output of the error
amplifier and CS_OUT is simultaneously disconnected
from the buffered LED current-sense output signal (Figure
5). When the internal dimming signal is high, the output
of the op amp is connected to COMP and CS_OUT is
connected to the buffered LED current-sense signal at
the same time (Figure 4). This enables the compensation
capacitor to hold the charge when the DIM signal has
turned off the internal switching MOSFET gate drive.
To maintain the charge on the compensation capacitors
CCOMP1 and CCOMP2, the capacitors should be of the
low-leakage ceramic type.
When the internal dimming signal is enabled, the volt-
age on the compensation capacitor forces the converter
into steady state almost instantaneously. The voltage on
COMP is subtracted from the internal slope compensation
signal and is then connected to one of the inputs of the
PWM comparator. The PWM comparator input is of the
CMOS type with very low bias currents.
Figure 5. Internal Error Amplifier Connections (Dimming Signal Low)
Figure 4. Internal Error Amplifier Connection (Dimming Signal High)
REFI
COMP
OUT
STATE B
X1
EA
RCOMP2
RCOMP1
CCOMP1
CCOMP2
REFI
COMP
OUT
RCOMP2
RCOMP1
CCOMP1
CCOMP2
STATE A
X1
EA
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11
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Analog Dimming
The MAX16812 offers analog dimming of the LED current
by allowing the application of an external voltage at REFI.
The output current is proportional to the voltage at REFI.
Use a potentiometer from REF or directly apply an exter-
nal voltage source at REFI.
PWM Comparator
The PWM comparator uses the instantaneous switch
current, the error-amplifier output, and the slope com-
pensation to determine when the gate drive DRV to the
internal n-channel switching MOSFET turns off. In normal
operation, gate drive DRV to the n-channel MOSFET
turns off when:
ISW x RSRC ≥ VCOMP - VOFFSET - VSCOMP
where ISW is the current through the internal n-channel
switching MOSFET, RSRC is the switch current-sense
resistor, VCOMP is the output voltage of the internal ampli-
fier, VOFFSET is the internal DC offset, which is a VBE
drop, and VSCOMP is the ramp function that starts at zero
and slews at the programmed slew rate (SR).
Internal Switching MOSFET Current Limit
The current-sense resistor (RSRC), connected between
the source of the internal MOSFET and ground, sets
the current limit. The SRC input has a voltage trip level
(VSRC) of 600mV for the cycle-by-cycle current limit. Use
the following equation to calculate the value RSRC:
SRC
SRC LXLIM
V
R
I
=
where ILXLIM is the peak current that flows through the
switching MOSFET at full load and low line. When the
voltage produced by this current (through the cur-
rent-sense resistor) exceeds the current-limit (ILIM) com-
parator threshold, the MOSFET driver (DRV) quickly
terminates the current on-cycle. The 200ns leading-edge
blanking circuit suppresses the leading-edge spike on
the current-sense waveform from appearing at the cur-
rent-limit comparator. There is also a hiccup comparator
(HICCUP) that limits the peak current in the internal
switch set at twice the peak limit setting.
Internal n-Channel
Switching MOSFET Driver (DRV)
L_REG provides power for the DRV output. Connect a
resistor from DRV to gate GT of the internal switching
MOSFET to control the switching MOSFET rise and fall
times, if necessary.
External Dimming
MOSFET Gate Drive (DGT)
DGT is the gate drive to the external dimming MOSFET
referenced to LV. H_REG provides the power to the gate
drive.
Overvoltage Protection
The overvoltage protection (OVP) comparator compares
the voltage at OV with a 1.238V (typ) internal reference.
When the voltage at OV exceeds the internal reference,
the OVP comparator terminates PWM switching and no
further energy is transferred to the load. Connect OV to
HV through a resistive voltage-divider to ground to set the
overvoltage threshold at the output.
Setting the Overvoltage Threshold
Connect OV to HV or to the high-side of the LEDs through
a resistive voltage-divider to set the overvoltage threshold
at the output (Figure 6).
Figure 6. OVP Setting
MAX16812
VLED+
AGND
OV
HV
ROV1
ROV2
MAX16812
VLED+
AGND
OV
ROV1
ROV2
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12
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
The overvoltage protection (OVP) comparator compares
the voltage at OV with a 1.238V (typ) internal reference.
Use the following equation to calculate resistorlues:
OV_LIM OV
OV1 OV2 OV
V V
R R x
V
−

=



where VOV is the 1.238V OV threshold. Choose ROV1
and ROV2 to be reasonably high-value resistors to pre-
vent the discharge of filter capacitors. This prevents
degraded performance during dimming.
Internal Oscillator Switching Frequency
The oscillator switching frequency is programmed by a
resistor connected from RT to AGND. To program the
oscillator frequency above 125kHz, choose the appropri-
ate resistor RT from the curves shown in the Oscillator
Frequency vs. RT graph in the Typical Operating
Characteristics section.
PWM Dimming
PWM dimming can be achieved by driving DIM with an
analog voltage less than VREF. See Figure 7. An external
resistor on TGRM from L_REG in conjunction with the
ramp capacitor, CTGRM, from TGRM to AGND creates a
sawtooth ramp that is compared with the DC voltage on
DIM. The output of the comparator is a pulsating dimming
signal. The frequency fRAMP of the sawtooth signal on
TGRM is given by:
RAMP
TGRM TGRM
3.67
f C R
≅×
Use the following formula to calculate the voltage VDIM,
necessary for a given output duty cycle, D:
VDIM = D x 1.238V
where VDIM is the DC voltage applied to DIM in volts.
The DC voltage for DIM can also be created by connect-
ing DIM to REF through a resistive voltage-divider. Using
the required dimming input voltage, VDIM, calculate the
resistor values for the divider string using the following
equation:
RDIM2 = [VDIM / (VREF - VDIM)] x RDIM1
where VREF is the voltage on REF.
PWM dimming can also be achieved by connecting
TGRM to a DC voltage less than VREF and applying the
PWM signal at DIM. The moment the internal dimming
signal goes low, gate drive DRV to the internal switching
MOSFET is turned off. The error amplifier goes to state
B (see the Internal Error Amplifier section and Figures 4
and 5). The peak current in the inductor prior to disabling
DRV is ILX. Gate drive DGT to the external dimming
MOSFET is held high. Then after a switchover period,
gate voltage VDGT on the external dimming MOSFET is
linearly controlled to reduce the LED current to 0. The fall
time of the LED current is controlled by an internal timing
circuit to 5µs for the MAX16812. During this period, the
gate (DRV) to the internal switching MOSFET is enabled.
After the fall time, the gate drive to the external dimming
MOSFET is turned off and the gate drive to the internal
switching MOSFET is still held high after the switchover
period. The peak current in the inductor is controlled at
ILX. Then after a time period of 20µs, the gate drive is
disabled. The scope shots in Figures 8–11 show the dim-
ming waveforms.
Figure 7. PWM Dimming from REF
MAX16812
AGND
DIM
REF
TGRM
L_REG
RDIM1 RTGRM
CTGRM
RDIM2
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13
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
When the DIM signal goes high, the LED current is grad-
ually increased to the programmed value. The rise time
of the LED current is controlled to 5µs for the MAX16812
by controlling the voltage on DGT. After the rise time, an
internal sensing circuit monitors the voltage across the
drain to the source of the external dimming MOSFET. The
LED current is now controlled at the programmed value
by a linear current regulating circuit. Once the voltage
across the drain to source of the dimming MOSFET drops
below 0.5V, the reference for the linear current regulating
circuit is increased to 1.1 times the programmed value.
The gate drive (DRV) to the internal switching MOSFET is
enabled and the error amplifier is returned to state A (see
the Internal Error Amplifier section and Figures 4 and 5).
Fault Protection
The MAX16812 features built-in overvoltage protection
and thermal shutdown. Connect a resistive voltage-di-
vider between HV, OV, and AGND to program the over-
voltage protection. In the case of a short circuit across
the LED string, the temperature of the external dimming
MOSFET could exceed the maximum allowable junction
temperature. This is due to excess power dissipation in the
MOSFET. Use the fault protection circuit shown in Figure
12 to protect the external dimming MOSFET.
Internal thermal shutdown in the MAX16812 safely turns
off the IC when the junction temperature exceeds +165°C.
Figure 11. LED Current, DIM Signal, and DRV Waveforms
when DIM Signal Goes High
Figure 10. LED Current, Output Voltage, and DRV Waveforms
when DIM Signal Goes High
Figure 9. LED Current, DIM Signal, and DRV Waveforms when
DIM Signal Goes Low
Figure 8. LED Current, Output Voltage, and DRV Waveforms
when DIM Signal Goes Low
MAX16812 fig11
10s/div
0V
VDRV
2V/div
0A, 0V
100mA/div
VDIM
5V/div
ILED
MAX16812 fig10
10s/div
ILED
VOUT
VDRV 0V
2V/div
0A, 0V
100mA/div
10V/div
MAX16812 fig09
10s/div
VDIM
5V/div
0V
VDRV
2V/div
0A, 0V
ILED
100mA/div
MAX16812 fig08
10s/div
ILED
VOUT
VDRV 0V
2V/div
0A, 0V
100mA/div
10V/div
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│
14
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Inductor Selection
The minimum required inductance is a function of the
operating frequency, the input-to-output voltage differen-
tial and the peak-to-peak inductor current (∆IL). Higher
∆IL allows for a lower inductor value while a lower ∆IL
requires a higher inductor value. A lower inductor value
minimizes size and cost, improves large-signal transient
response, but reduces efficiency due to higher peak
currents and higher peak-to-peak output ripple voltage
for the same output capacitor. On the other hand, higher
inductance increases efficiency by reducing the ripple
current, ∆IL. However, resistive losses due to the extra
turns can exceed the benefit gained from lower ripple cur-
rent levels, especially when the inductance is increased
without allowing for larger inductor dimensions. A good
compromise is to choose ∆IL equal to 30% of the full
load current. The inductor saturating current specification
is also important to avoid runaway current during output
overload and continuous short-circuit conditions.
Buck Configuration: In a buck configuration (Figure 13),
the average inductor current does not vary with the input.
The worst-case peak current occurs at the highest input
voltage. In this case, the inductance, L, for continuous
conduction mode given by:
( )
OUT INMAX OUT
INMAX SW L
V x V V
L V x f x I
−
=∆
where VINMAX is the maximum input voltage, fSW is the
switching frequency, and VOUT is the output voltage.
Boost Configuration: In the boost converter, the aver-
age inductor current varies with the input voltage and the
maximum average current occurs at the lowest input volt-
age. For the boost converter, the average inductor current
is equal to the input current. In this case, the inductance,
L, is calculated as:
( )
INMIN OUT INMIN
OUT SW L
V x V V
L V x f x I
−
=∆
where VINMIN is the minimum input voltage, VOUT is the
output voltage, and fSW is the switching frequency. See
Figure 14.
Buck-Boost Configuration: In a buck-boost converter
(see the Typical Application Circuit), the average inductor
current is equal to the sum of the input current and the
LED current. In this case, the inductance, L, is:
( )
OUT INMIN
OUT INMIN SW L
V x V
L
V V x f x I
=
+∆
where VINMIN is the minimum input voltage, VOUT is the
output voltage, and fSW is the switching frequency.
Figure 12. Dimming MOSFET Protection
MAX6501
GND
4.7F
100k
5.1V
ZENER
GND
VCC
TO L_REG PIN
OF MAX16812
TO EN PIN OF
MAX16812
VIN
TOVER
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│
15
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Figure 14. Boost Configuration
Figure 13. Buck Configuration
MAX16812
LV SRC
IN
RT
EN
TGRM
L_REG
CS- CS+ DGT DD H_REG HV LX
RCS
RRT
RTGRM
CH_REG
CL_REG
CREF
ROV1
RCOMP1
RREF1
RREF2
RCOMP2
CCOMP1
CCOMP2
VOUT
VIN
ROV2
GT
DRV
SLP
COMP
OV SGND AGND REFI
REF FBCS_OUT
VIN
CIN1
COUT
DIM
CTGRM
CSLP
DOUT
RSRC
RG
VOUT
MAX16812
H_REG
EN
RT
TGRM
L_REG
HV LX LV DD DGT CS- CS+
RRT
RTGRM
CL_REG
CH_REG
CREF
ROV1
RCOMP1
RREF1
RREF2
RCOMP2
CCOMP1
CCOMP2
VOUT
ROV2
GT
DRV
SLP
COMP
OV SGND AGND REFI
REF FBCS_OUT
VIN
DIM
CTGRM
CIN
CSLP
RG
SRC
RSRC
DOUT RCS
COUT
IN
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16
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Output Capacitor
The function of the output capacitor is to reduce the out-
put ripple to acceptable levels. The ESR, ESL, and the
bulk capacitance of the output capacitor contribute to the
output ripple. In most of the applications, the output ESR
and ESL effects can be dramatically reduced by using
low-ESR ceramic capacitors. To reduce the ESL effects,
connect multiple ceramic capacitors in parallel to achieve
the required capacitance.
In a buck configuration, the output capacitance, COUT, is
calculated using the follow equation:
INMAX OUT OUT
OUT 2
R INMAX SW
( V V ) V
C
V 2 L V f
−×
≥∆ ×× × ×
where ∆VR is the maximum allowable output ripple.
In a boost configuration, the output capacitance, COUT,
is calculated as:
OUT INMIN OUT
OUT R OUT SW
( V V ) 2 I
C V V f
− ××
≥∆× ×
where COUT is the output capacitor.
In a buck-boost configuration, the output capacitance,
COUT is:
OUT OUT
OUT
R OUT INMIN SW
2 V I
C
V (V V ) f
××
≥∆× + ×
where VOUT is the voltage across the load and IOUT is
the output current.
Input Capacitor
An input capacitor connected between IN and ground
must be used when configuring the MAX16812 as a buck
converter. Use a low-ESR input capacitor that can handle
the maximum input RMS ripple current. Calculate the
maximum RMS ripple using the follow equation:
OUT OUT INMIN OUT
IN(RMS)
INMIN
I V (V - V )
I
V
××
=
When using the MAX16812 in a boost or buck-boost con-
figuration, the input capacitor’s RMS current is low and
the input capacitance can be small. However, an addi-
tional electrolytic capacitor may be required to prevent
oscillations due to line impedances.
Figure 15. SEPIC Configuration
MAX16812
CS-
CS+
DGT
DD
H_REG
HV
LX
OV
SGND
AGND
REFI
FB
REF
CS_OUT
RREF2
CH_REG
L2
L1
RREF1
CSLP
COUT
CS
RG
RCOMP1
RCOMP2
ROV1
ROV2
RSRC
VOUT
RT
CL_REG
RCS
RTGRM
COMP
SLP
SRC
GT
DRV
CCOMP1
CCOMP2
DOUT
VOUT
VIN
CIN1
CTGRM
LV
VIN
IN
L_REG
TGRM
DIM
EN
RT
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17
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Layout Recommendations
Typically, there are two sources of noise emission in a
switching power supply: high di/dt loops and high dv/dt
surfaces. For example, traces that carry the drain current
often form high di/dt loops. Similarly, the drain of the
internal MOSFET connected to the LX pin presents a dv/
dt source. Keep all PCB traces carrying switching cur-
rents as short as possible to minimize current loops. Use
ground planes for best results.
Careful PCB layout is critical to achieve low switching
losses and clean, stable operation. Use a multilayer board
whenever possible for better noise immunity and power
dissipation. Follow these guidelines for good PCB layout:
●Use a large copper plane under the MAX16812 pack-
age. Ensure that all heat-dissipating components
have adequate cooling. Connect the exposed pad of
the device to the ground plane.
●Isolate the power components and high-current paths
from sensitive analog circuitry.
●Keep the high-current paths short, especially at the
ground terminals. This practice is essential for stable,
jitter-free operation. Keep switching loops short.
●Connect AGND and SGND to a ground plane.
Ensure a low-impedance connection between all
ground points.
●Keep the power traces and load connections short.
This practice is essential for high efficiency. Use thick
copper PCBs to enhance full-load efficiency.
●Ensure that the feedback connection to FB is short
and direct.
●Route high-speed switching nodes away from the
sensitive analog areas.
●To prevent discharge of the compensation capacitors,
CCOMP1 and CCOMP2, during the off-time of the dim-
ming cycle, ensure that the PCB area close to these
components has extremely low leakage.
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18
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
PACKAGE
TYPE
PACKAGE
CODE
OUTLINE
NO.
LAND
PATTERN NO.
28 TQFN-EP T2855+8 21-0140 90-0028
MAX16812
TQFN
+
TOP VIEW
26
27
25
24
10
9
11
COMP
REF
CS_OUT
AGND
EN
12
FB
LX
DRV
HV
LX
H_REG
LV
1 2
TGRM
4 5 6 7
2021 19 17 16 15
DIM
RT
DGT
DD
SGND
L_REG
REFI GT
3
18
28 8
OV IN
*EP
*EP = EXPOSED PAD
SLP
23 13 CS+
SRC
22 14 CS-
SRC
MAX16812
LV
BUCK-BOOST CONFIGURATION
SRC
IN
RT
EN
TGRM
L_REG
CS- CS+ DGT DD H_REG HV LX
RCS
RT
RTGRM
CH_REG
CL_REG
ROV1
RCOMP1
RREF1
RREF2
CREF
RCOMP2
CCOMP1
CCOMP2
VOUT
ROV2
GT
DRV
SLP
COMP
OV SGND AGND REFI
REF FBCS_OUT
VIN
CIN1
COUT
DIM
CTGRM
CSLP
DOUT
RSRC
RG
VOUT
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19
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
Chip Information
PROCESS: BiCMOS
TRANSISTOR COUNT: 8699
Pin Conguration
Typical Application Circuit
Package Information
For the latest package outline information and land patterns
(footprints), go to www.maximintegrated.com/packages. Note
that a “+”, “#”, or “-” in the package code indicates RoHS status
only. Package drawings may show a different suffix character, but
the drawing pertains to the package regardless of RoHS status.
REVISION
NUMBER
REVISION
DATE DESCRIPTION PAGES
CHANGED
0 7/07 Initial release —
1 4/14 No /V OPNs; removed Automotive reference from Applications section 1
Maxim Integrated cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim Integrated product. No circuit patent licenses
are implied. Maxim Integrated reserves the right to change the circuitry and specications without notice at any time. The parametric values (min and max limits)
shown in the Electrical Characteristics table are guaranteed. Other parametric values quoted in this data sheet are provided for guidance.
Maxim Integrated and the Maxim Integrated logo are trademarks of Maxim Integrated Products, Inc.
MAX16812 Integrated High-Voltage LED Driver
with Analog and PWM Dimming Control
© 2014 Maxim Integrated Products, Inc.
│
20
Revision History
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