LMC660
CMOS Quad Operational Amplifier
General Description
The LMC660 CMOS Quad operational amplifier is ideal for
operation from a single supply. It operates from +5V to +15V
and features rail-to-rail output swing in addition to an input
common-mode range that includes ground. Performance
limitations that have plagued CMOS amplifiers in the past
are not a problem with this design. Input V
OS
, drift, and
broadband noise as well as voltage gain into realistic loads
(2 kΩand 600Ω) are all equal to or better than widely ac-
cepted bipolar equivalents.
This chip is built with National’s advanced Double-Poly
Silicon-Gate CMOS process.
See the LMC662 datasheet for a dual CMOS operational
amplifier with these same features.
Features
nRail-to-rail output swing
nSpecified for 2 kΩand 600Ωloads
nHigh voltage gain: 126 dB
nLow input offset voltage: 3 mV
nLow offset voltage drift: 1.3 µV/˚C
nUltra low input bias current: 2 fA
nInput common-mode range includes V
−
nOperating range from +5V to +15V supply
nI
SS
= 375 µA/amplifier; independent of V
+
nLow distortion: 0.01% at 10 kHz
nSlew rate: 1.1 V/µs
nAvailable in extended temperature range (−40˚C to
+125˚C); ideal for automotive applications
nAvailable to Standard Military Drawing specification
Applications
nHigh-impedance buffer or preamplifier
nPrecision current-to-voltage converter
nLong-term integrator
nSample-and-Hold circuit
nPeak detector
nMedical instrumentation
nIndustrial controls
nAutomotive sensors
Connection Diagram
14-Pin DIP/SO
DS008767-1
LMC660 Circuit Topology (Each Amplifier)
DS008767-4
August 2000
LMC660 CMOS Quad Operational Amplifier
© 2000 National Semiconductor Corporation DS008767 www.national.com
Absolute Maximum Ratings (Note 3)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Differential Input Voltage ±Supply Voltage
Supply Voltage 16V
Output Short Circuit to V
+
(Note 12)
Output Short Circuit to V
−
(Note 1)
Lead Temperature
(Soldering, 10 sec.) 260˚C
Storage Temp. Range −65˚C to +150˚C
Voltage at Input/Output Pins (V
+
) + 0.3V, (V
−
) − 0.3V
Current at Output Pin ±18 mA
Current at Input Pin ±5mA
Current at Power Supply Pin 35 mA
Power Dissipation (Note 2)
Junction Temperature 150˚C
ESD tolerance (Note 8) 1000V
Operating Ratings
Temperature Range
LMC660AI −40˚C ≤T
J
≤+85˚C
LMC660C 0˚C ≤T
J
≤+70˚C
Supply Voltage Range 4.75V to 15.5V
Power Dissipation (Note 10)
Thermal Resistance (θ
JA
) (Note 11)
14-Pin Molded DIP 85˚C/W
14-Pin SO 115˚C/W
DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T
J
= 25˚C. Boldface limits apply at the temperature extremes. V
+
=
5V, V
−
= 0V, V
CM
= 1.5V, V
O
= 2.5V and R
L
>1M unless otherwise specified.
Parameter Conditions Typ
(Note 4) LMC660AI LMC660C Units
Limit Limit
(Note 4) (Note 4)
Input Offset Voltage 1 3 6 mV
3.3 6.3 max
Input Offset Voltage 1.3 µV/˚C
Average Drift
Input Bias Current 0.002 pA
42max
Input Offset Current 0.001 pA
21max
Input Resistance >1 TeraΩ
Common Mode 0V ≤V
CM
≤12.0V 83 70 63 dB
Rejection Ratio V
+
= 15V 68 62 min
Positive Power Supply 5V ≤V
+
≤15V 83 70 63 dB
Rejection Ratio V
O
= 2.5V 68 62 min
Negative Power Supply 0V ≤V
−
≤−10V 94 84 74 dB
Rejection Ratio 83 73 min
Input Common-Mode V
+
= 5V & 15V −0.4 −0.1 −0.1 V
Voltage Range For CMRR ≥50 dB 00max
V
+
− 1.9 V
+
− 2.3 V
+
− 2.3 V
V
+
− 2.5 V
+
− 2.4 min
Large Signal R
L
=2kΩ(Note 5) 2000 440 300 V/mV
Voltage Gain Sourcing 400 200 min
Sinking 500 180 90 V/mV
120 80 min
R
L
= 600Ω(Note 5) 1000 220 150 V/mV
Sourcing 200 100 min
Sinking 250 100 50 V/mV
60 40 min
LMC660
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DC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for T
J
= 25˚C. Boldface limits apply at the temperature extremes. V
+
=
5V, V
−
= 0V, V
CM
= 1.5V, V
O
= 2.5V and R
L
>1M unless otherwise specified.
Parameter Conditions Typ
(Note 4) LMC660AI LMC660C Units
Limit Limit
(Note 4) (Note 4)
Output Swing V
+
= 5V 4.87 4.82 4.78 V
R
L
=2kΩto V
+
/2 4.79 4.76 min
0.10 0.15 0.19 V
0.17 0.21 max
V
+
= 5V 4.61 4.41 4.27 V
R
L
= 600Ωto V
+
/2 4.31 4.21 min
0.30 0.50 0.63 V
0.56 0.69 max
V
+
= 15V 14.63 14.50 14.37 V
R
L
=2kΩto V
+
/2 14.44 14.32 min
0.26 0.35 0.44 V
0.40 0.48 max
V
+
= 15V 13.90 13.35 12.92 V
R
L
= 600Ωto V
+
/2 13.15 12.76 min
0.79 1.16 1.45 V
1.32 1.58 max
Output Current Sourcing, V
O
=0V221613mA
V
+
=5V 14 11 min
Sinking, V
O
=5V211613mA
14 11 min
Output Current Sourcing, V
O
=0V402823mA
V
+
= 15V 25 21 min
Sinking, V
O
= 13V 39 28 23 mA
(Note 12) 24 20 min
Supply Current All Four Amplifiers 1.5 2.2 2.7 mA
V
O
= 1.5V 2.6 2.9 max
AC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T
J
= 25˚C. Boldface limits apply at the temperature extremes. V
+
=
5V, V
−
= 0V, V
CM
= 1.5V, V
O
= 2.5V and R
L
>1M unless otherwise specified.
Parameter Conditions Typ
(Note 4) LMC660AI LMC660C Units
Limit Limit
(Note 4) (Note 4)
Slew Rate (Note 6) 1.1 0.8 0.8 V/µs
0.6 0.7 min
Gain-Bandwidth Product 1.4 MHz
Phase Margin 50 Deg
Gain Margin 17 dB
Amp-to-Amp Isolation (Note 7) 130 dB
Input Referred Voltage Noise F = 1 kHz 22
Input Referred Current Noise F = 1 kHz 0.0002
LMC660
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AC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for T
J
= 25˚C. Boldface limits apply at the temperature extremes. V
+
=
5V, V
−
= 0V, V
CM
= 1.5V, V
O
= 2.5V and R
L
>1M unless otherwise specified.
Parameter Conditions Typ
(Note 4) LMC660AI LMC660C Units
Limit Limit
(Note 4) (Note 4)
Total Harmonic Distortion F = 10 kHz,
A
V
= −10
R
L
=2kΩ,
V
O
=8V
PP
V
+
= 15V
0.01 %
Note 1: Applies to both single supply and split supply operation. Continuous short circuit operation at elevated ambient temperature and/or multiple Op Amp shorts
can result in exceeding the maximum allowed junction temperature of 150˚C. Output currents in excess of ±30 mA over long term may adversely affect reliability.
Note 2: The maximum power dissipation is a function of TJ(max),θJA, and TA. The maximum allowable power dissipation at any ambient temperature is PD=(T
J(max)
−T
A
)/θJA.
Note 3: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is in-
tended to be functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics. The
guaranteed specifications apply only for the test conditions listed.
Note 4: Typical values represent the most likely parametric norm. Limits are guaranteed by testing or correlation.
Note 5: V+= 15V, VCM = 7.5V and RLconnected to 7.5V. For Sourcing tests, 7.5V ≤VO≤11.5V. For Sinking tests, 2.5V ≤VO≤7.5V.
Note 6: V+= 15V. Connected as Voltage Follower with 10V step input. Number specified is the slower of the positive and negative slew rates.
Note 7: Input referred. V+= 15V and RL=10kΩconnected to V+/2. Each amp excited in turn with 1 kHz to produce VO=13V
PP.
Note 8: Human body model, 1.5 kΩin series with 100 pF.
Note 9: Amilitary RETS electrical test specification is available on request.At the time of printing, the LMC660AMJ/883 RETS spec complied fully with the boldface
limits in this column. The LMC660AMJ/883 may also be procured to a Standard Military Drawing specification.
Note 10: For operating at elevated temperatures the device must be derated based on the thermal resistance θJA with PD=(T
J−T
A
)/θJA.
Note 11: All numbers apply for packages soldered directly into a PC board.
Note 12: Do not connect output to V+when V+is greater than 13V or reliability may be adversely affected.
Typical Performance Characteristics V
S
=±7.5V, T
A
= 25˚C unless otherwise specified
Supply Current
vs Supply Voltage
DS008767-24
Offset Voltage
DS008767-25
Input Bias Current
DS008767-26
Output Characteristics
Current Sinking
DS008767-27
Output Characteristics
Current Sourcing
DS008767-28
Input Voltage Noise
vs Frequency
DS008767-29
LMC660
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Typical Performance Characteristics V
S
=±7.5V, T
A
= 25˚C unless otherwise specified (Continued)
Note: Avoid resistive loads of less than 500Ω, as they may cause instability.
Application Hints
Amplifier Topology
The topology chosen for the LMC660, shown in
Figure 1
,is
unconventional (compared to general-purpose op amps) in
that the traditional unity-gain buffer output stage is not used;
instead, the output is taken directly from the output of the in-
tegrator, to allow rail-to-rail output swing. Since the buffer
traditionally delivers the power to the load, while maintaining
high op amp gain and stability, and must withstand shorts to
either rail, these tasks now fall to the integrator.
As a result of these demands, the integrator is a compound
affair with an embedded gain stage that is doubly fed forward
(via C
f
and Cff) by a dedicated unity-gain compensation
driver. In addition, the output portion of the integrator is a
push-pull configuration for delivering heavy loads. While
sinking current the whole amplifier path consists of three
gain stages with one stage fed forward, whereas while
sourcing the path contains four gain stages with two fed
forward.
The large signal voltage gain while sourcing is comparable
to traditional bipolar op amps, even with a 600Ωload. The
gain while sinking is higher than most CMOS op amps, due
to the additional gain stage; however, under heavy load
(600Ω) the gain will be reduced as indicated in the Electrical
Characteristics.
Compensating Input Capacitance
The high input resistance of the LMC660 op amps allows the
use of large feedback and source resistor values without los-
ing gain accuracy due to loading. However, the circuit will be
especially sensitive to its layout when these large-value re-
sistors are used.
CMRR vs Frequency
DS008767-30
Open-Loop Frequency
Response
DS008767-31
Frequency Response
vs Capacitive Load
DS008767-32
Non-Inverting Large Signal
Pulse Response
DS008767-33
Stability vs
Capacitive Load
DS008767-34
Stability vs
Capacitive Load
DS008767-35
DS008767-4
FIGURE 1. LMC660 Circuit Topology (Each Amplifier)
LMC660
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Application Hints (Continued)
Every amplifier has some capacitance between each input
and AC ground, and also some differential capacitance be-
tween the inputs. When the feedback network around an
amplifier is resistive, this input capacitance (along with any
additional capacitance due to circuit board traces, the
socket, etc.) and the feedback resistors create a pole in the
feedback path. In the following General OperationalAmplifier
circuit,
Figure 2
the frequency of this pole is
where C
S
is the total capacitance at the inverting input, in-
cluding amplifier input capcitance and any stray capacitance
from the IC socket (if one is used), circuit board traces, etc.,
and R
P
is the parallel combination of R
F
and R
IN
. This for-
mula, as well as all formulae derived below, apply to invert-
ing and non-inverting op-amp configurations.
When the feedback resistors are smaller than a few kΩ, the
frequency of the feedback pole will be quite high, since C
S
is
generally less than 10 pF. If the frequency of the feedback
pole is much higher than the “ideal” closed-loop bandwidth
(the nominal closed-loop bandwidth in the absence of C
S
),
the pole will have a negligible effect on stability, as it will add
only a small amount of phase shift.
However, if the feedback pole is less than approximately 6 to
10 times the “ideal” −3 dB frequency, a feedback capacitor,
C
F
, should be connected between the output and the invert-
ing input of the op amp. This condition can also be stated in
terms of the amplifier’s low-frequency noise gain: To main-
tain stability a feedback capacitor will probably be needed if
where
is the amplifier’s low-frequency noise gain and GBW is the
amplifier’s gain bandwidth product. An amplifier’s low-
frequency noise gain is represented by the formula
regardless of whether the amplifier is being used in inverting
or non-inverting mode. Note that a feedback capacitor is
more likely to be needed when the noise gain is low and/or
the feedback resistor is large.
If the above condition is met (indicating a feedback capacitor
will probably be needed), and the noise gain is large enough
that:
the following value of feedback capacitor is recommended:
If
the feedback capacitor should be:
Note that these capacitor values are usually significant
smaller than those given by the older, more conservative for-
mula:
Using the smaller capacitors will give much higher band-
width with little degradation of transient response. It may be
necessary in any of the above cases to use a somewhat
larger feedback capacitor to allow for unexpected stray ca-
pacitance, or to tolerate additional phase shifts in the loop, or
excessive capacitive load, or to decrease the noise or band-
width, or simply because the particular circuit implementa-
tion needs more feedback capacitance to be sufficiently
stable. For example, a printed circuit board’s stray capaci-
tance may be larger or smaller than the breadboard’s, so the
actual optimum value for C
F
may be different from the one
estimated using the breadboard. In most cases, the values
of C
F
should be checked on the actual circuit, starting with
the computed value.
Capacitive Load Tolerance
Like many other op amps, the LMC660 may oscillate when
its applied load appears capacitive. The threshold of oscilla-
tion varies both with load and circuit gain. The configuration
most sensitive to oscillation is a unity-gain follower. See
Typical Performance Characteristics.
The load capacitance interacts with the op amp’s output re-
sistance to create an additional pole. If this pole frequency is
sufficiently low, it will degrade the op amp’s phase margin so
that the amplifier is no longer stable at low gains. As shown
in
Figure 3
, the addition of a small resistor (50Ωto 100Ω)in
series with the op amp’s output, and a capacitor (5 pF to
10 pF) from inverting input to output pins, returns the phase
margin to a safe value without interfering with lower-
frequency circuit operation. Thus larger values of capaci-
tance can be tolerated without oscillation. Note that in all
cases, the output will ring heavily when the load capacitance
is near the threshold for oscillation.
DS008767-6
CSconsists of the amplifier’s input capacitance plus any stray capacitance
from the circuit board and socket. CFcompensates for the pole caused by
CSand the feedback resistors.
FIGURE 2. General Operational Amplifier Circuit
LMC660
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Application Hints (Continued)
Capacitive load driving capability is enhanced by using a pull
up resistor to V
+
(
Figure 4
). Typically a pull up resistor con-
ducting 500 µA or more will significantly improve capacitive
load responses. The value of the pull up resistor must be de-
termined based on the current sinking capability of the ampli-
fier with respect to the desired output swing. Open loop gain
of the amplifier can also be affected by the pull up resistor
(see Electrical Characteristics).
PRINTED-CIRCUIT-BOARD LAYOUT
FOR HIGH-IMPEDANCE WORK
It is generally recognized that any circuit which must operate
with less than 1000 pA of leakage current requires special
layout of the PC board. When one wishes to take advantage
of the ultra-low bias current of the LMC662, typically less
than 0.04 pA, it is essential to have an excellent layout. For-
tunately, the techniques for obtaining low leakages are quite
simple. First, the user must not ignore the surface leakage of
the PC board, even though it may sometimes appear accept-
ably low, because under conditions of high humidity or dust
or contamination, the surface leakage will be appreciable.
To minimize the effect of any surface leakage, lay out a ring
of foil completely surrounding the LMC660’s inputs and the
terminals of capacitors, diodes, conductors, resistors, relay
terminals, etc. connected to the op-amp’s inputs. See
Figure
5
. To have a significant effect, guard rings should be placed
on both the top and bottom of the PC board. This PC foil
must then be connected to a voltage which is at the same
voltage as the amplifier inputs, since no leakage current can
flow between two points at the same potential. For example,
a PC board trace-to-pad resistance of 10
12
Ω, which is nor-
mally considered a very large resistance, could leak 5 pA if
the trace were a 5V bus adjacent to the pad of an input. This
would cause a 100 times degradation from the LMC660’s ac-
tual performance. However, if a guard ring is held within
5 mV of the inputs, then even a resistance of 10
11
Ωwould
cause only 0.05 pA of leakage current, or perhaps a minor
(2:1) degradation of the amplifier’s performance. See
Figure
6a
,
Figure 6b
,
Figure 6c
for typical connections of guard
rings for standard op-amp configurations. If both inputs are
active and at high impedance, the guard can be tied to
ground and still provide some protection; see
Figure 6d
.
DS008767-5
FIGURE 3. Rx, Cx Improve Capacitive Load Tolerance
DS008767-23
FIGURE 4. Compensating for Large Capacitive Loads
with a Pull Up Resistor
DS008767-16
FIGURE 5. Example, using the LMC660,
of Guard Ring in P.C. Board Layout
LMC660
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Application Hints (Continued)
The designer should be aware that when it is inappropriate
to lay out a PC board for the sake of just a few circuits, there
is another technique which is even better than a guard ring
on a PC board: Don’t insert the amplifier’s input pin into the
board at all, but bend it up in the air and use only air as an in-
sulator. Air is an excellent insulator. In this case you may
have to forego some of the advantages of PC board con-
struction, but the advantages are sometimes well worth the
effort of using point-to-point up-in-the-air wiring. See
Figure
7
.
BIAS CURRENT TESTING
The test method of
Figure 8
is appropriate for bench-testing
bias current with reasonable accuracy. To understand its op-
eration, first close switch S2 momentarily. When S2 is
opened, then
A suitable capacitor for C2 would bea5pFor10pFsilver
mica, NPO ceramic, or air-dielectric. When determining the
magnitude of I
b
−, the leakage of the capacitor and socket
must be taken into account. Switch S2 should be left shorted
most of the time, or else the dielectric absorption of the ca-
pacitor C2 could cause errors.
Similarly, if S1 is shorted momentarily (while leaving S2
shorted)
where C
x
is the stray capacitance at the + input.
DS008767-17
(a) Inverting Amplifier
DS008767-18
(b) Non-Inverting Amplifier
DS008767-19
(c) Follower
DS008767-20
(d) Howland Current Pump
FIGURE 6. Guard Ring Connections
DS008767-21
(Input pins are lifted out of PC board and soldered directly to components.
All other pins connected to PC board.)
FIGURE 7. Air Wiring
DS008767-22
FIGURE 8. Simple Input Bias Current Test Circuit
LMC660
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Typical Single-Supply Applications (V
+
= 5.0 VDC)
Additional single-supply applications ideas can be found in
the LM324 datasheet. The LMC660 is pin-for-pin compatible
with the LM324 and offers greater bandwidth and input resis-
tance over the LM324. These features will improve the per-
formance of many existing single-supply applications. Note,
however, that the supply voltage range of the LMC660 is
smaller than that of the LM324.
If R1 = R5, R3 = R6, and R4 = R7; then
∴A
V
≈100 for circuit shown.
For good CMRR over temperature, low drift resistors should
be used. Matching of R3 to R6 and R4 to R7 affect CMRR.
Gain may be adjusted through R2. CMRR may be adjusted
through R7.
Oscillator frequency is determined by R1, R2, C1, and C2:
fosc = 1/2πRC, where R = R1 = R2 and
C=C1=C2.
This circuit, as shown, oscillates at 2.0 kHz with a peak-to-
peak output swing of 4.5V.
Low-Leakage Sample-and-Hold
DS008767-7
Instrumentation Amplifier
DS008767-8
Sine-Wave Oscillator
DS008767-9
1 Hz Square-Wave Oscillator
DS008767-10
Power Amplifier
DS008767-11
LMC660
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Typical Single-Supply Applications
(V+= 5.0 VDC) (Continued)
Ordering Information
Package Temperature Range NSC
Drawing Transport
Media
Industrial Commercial
−40˚C to +85˚C 0˚C to +70˚C
14-Pin LMC660AIM LMC660CM M14A Rail
Small Outline LMC660AIMX LMC660CMX Tape and Reel
14-Pin LMC660AIN LMC660CN N14A Rail
Molded DIP
10 Hz Bandpass Filter
DS008767-12
fO=10Hz
Q = 2.1
Gain = −8.8
10 Hz High-Pass Filter
DS008767-13
fc=10Hz
d = 0.895
Gain = 1
2 dB passband ripple
1 Hz Low-Pass Filter
(Maximally Flat, Dual Supply Only)
DS008767-14
fc=1Hz
d = 1.414
Gain = 1.57
High Gain Amplifier with Offset
Voltage Reduction
DS008767-15
Gain = −46.8
Output offset voltage reduced to the level of the input offset voltage of the
bottom amplifier (typically 1 mV).
LMC660
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Physical Dimensions inches (millimeters) unless otherwise noted
Small Outline Dual-In-Line Pkg. (M)
Order Number LMC660AIM, LMC660CM or LMC660AIMX
NS Package Number M14A
Molded Dual-In-Line Pkg. (N)
Order Number LMC660AIN, LMC660CN or LMC660CNX
NS Package Number N14A
LMC660
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Notes
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NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT
DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL
COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:
1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant
into the body, or (b) support or sustain life, and
whose failure to perform when properly used in
accordance with instructions for use provided in the
labeling, can be reasonably expected to result in a
significant injury to the user.
2. A critical component is any component of a life
support device or system whose failure to perform
can be reasonably expected to cause the failure of
the life support device or system, or to affect its
safety or effectiveness.
National Semiconductor
Corporation
Americas
Tel: 1-800-272-9959
Fax: 1-800-737-7018
Email: support@nsc.com
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Email: europe.support@nsc.com
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Email: nsj.crc@jksmtp.nsc.com
Fax: 81-3-5639-7507
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LMC660 CMOS Quad Operational Amplifier
National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.
