LM35DZLFT4 - NATIONAL SEMICONDUCTOR

LM359

LM359 Dual, High Speed, Programmable, Current Mode (Norton) Amplifiers

Literature Number: SNOSBT4B

LM359

Dual, High Speed, Programmable, Current Mode (Norton)

Amplifiers

General Description

The LM359 consists of two current differencing (Norton)

input amplifiers. Design emphasis has been placed on ob-

taining high frequency performance and providing user pro-

grammable amplifier operating characteristics. Each ampli-

fier is broadbanded to provide a high gain bandwidth

product, fast slew rate and stable operation for an inverting

closed loop gain of 10 or greater. Pins for additional external

frequency compensation are provided. The amplifiers are

designed to operate from a single supply and can accom-

modate input common-mode voltages greater than the sup-

ply.

Applications

nGeneral purpose video amplifiers

nHigh frequency, high Q active filters

nPhoto-diode amplifiers

nWide frequency range waveform generation circuits

nAll LM3900 AC applications work to much higher

frequencies

Features

nUser programmable gain bandwidth product, slew rate,

input bias current, output stage biasing current and total

device power dissipation

nHigh gain bandwidth product (I

SET

= 0.5 mA)

400 MHz for A

=10to100

30 MHz for A

nHigh slew rate (I

SET

= 0.5 mA)

60 V/µs for A

=10to100

30 V/µs for A

nCurrent differencing inputs allow high common-mode

input voltages

nOperates from a single 5V to 22V supply

nLarge inverting amplifier output swing, 2 mV to V

−

nLow spot noise, for f >1 kHz

Typical Application

00778801

•A

=20dB

•−3 dB bandwidth = 2.5 Hz to 25 MHz

•Differential phase error <1˚ at 3.58 MHz

•Differential gain error <0.5% at 3.58 MHz

Connection Diagram

Dual-In-Line Package

00778802

Top View

Order Number LM359M or LM359N

See NS Package Number M14A or N14A

August 2000

LM359 Dual, High Speed, Programmable, Current Mode (Norton) Amplifiers

Absolute Maximum Ratings (Note 1)

If Military/Aerospace specified devices are required,

please contact the National Semiconductor Sales Office/

Distributors for availability and specifications.

Supply Voltage 22 V

or ±11 V

Power Dissipation (Note 2)

J Package 1W

N Package 750 mW

Maximum T

J Package +150˚C

N Package +125˚C

Thermal Resistance

J Package

147˚C/W still air

110˚C/W with 400 linear feet/min air flow

N Package

100˚C/W still air

75˚C/W with 400 linear feet/min air flow

Input Currents, I

(+) or I

(−) 10 mA

Set Currents, I

SET(IN)

or I

SET(OUT)

2mA

Operating Temperature Range

LM359 0˚C to +70˚C

Storage Temperature Range −65˚C to +150˚C

Lead Temperature

(Soldering, 10 sec.) 260˚C

Soldering Information

Dual-In-Line Package

Soldering (10 sec.) 260˚C

Small Outline Package

Vapor Phase (60 sec.) 215˚C

Infrared (15 sec.) 220˚C

See AN-450 “Surface Mounting Methods and Their Effect

on Product Reliability” for other methods of soldering

surface mount devices.

ESD rating to be determined.

Electrical Characteristics

SET(IN)

SET(OUT)

= 0.5 mA, V

supply

= 12V, T

= 25˚C unless otherwise noted

Parameter Conditions LM359 Units

Min Typ Max

Open Loop Voltage V

supply

= 12V, R

= 1k, f = 100 Hz 62 72 dB

Gain T

= 125˚C 68 dB

Bandwidth R

=1kΩ,C

comp

=10pF 15 30 MHz

Unity Gain

Gain Bandwidth Product R

=50Ωto 200Ω200 400 MHz

Gain of 10 to 100

Slew Rate

Unity Gain R

=1kΩ,C

comp

= 10 pF 30 V/µs

Gain of 10 to 100 R

<200Ω60 V/µs

Amplifier to Amplifier f = 100 Hz to 100 kHz, R

= 1k −80 dB

Coupling

Mirror Gain at 2 mA I

(+), I

SET

= 5 µA, T

= 25˚C 0.9 1.0 1.1 µA/µA

(Note 3) at 0.2 mA I

(+), I

SET

= 5 µA 0.9 1.0 1.1 µA/µA

Over Temp.

at 20 µA I

(+), I

SET

= 5 µA 0.9 1.0 1.1 µA/µA

Over Temp.

∆Mirror Gain at 20 µA to 0.2 mA I

(+) 3 5 %

(Note 3) Over Temp, I

SET

=5µA

Input Bias Current Inverting Input, T

= 25˚C 8 15 µA

Over Temp. 30 µA

Input Resistance (βre) Inverting Input 2.5 kΩ

Output Resistance I

OUT

=15mArms,f=1MHz 3.5 Ω

Output Voltage Swing R

= 600Ω

OUT

High I

(−) and I

(+) Grounded 9.5 10.3 V

OUT

Low I

(−) = 100 µA, I

(+)=0 2 50 mV

LM359

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Electrical Characteristics (Continued)

SET(IN)

SET(OUT)

= 0.5 mA, V

supply

= 12V, T

= 25˚C unless otherwise noted

Parameter Conditions LM359 Units

Min Typ Max

Output Currents

Source I

(−) and I

(+) Grounded, R

= 100Ω16 40 mA

Sink (Linear Region) V

comp

−0.5V = V

OUT

= 1V, I

(+) = 0 4.7 mA

Sink (Overdriven) I

(−) = 100 µA, I

(+) = 0, 1.5 3 mA

OUT

Force = 1V

Supply Current Non-Inverting Input 18.5 22 mA

Grounded, R

=∞

Power Supply Rejection f = 120 Hz, I

(+) Grounded 40 50 dB

(Note 4)

Note 1: “Absolute Maximum Ratings” indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is

functional, but do not guarantee specific performance limits.

Note 2: See Maximum Power Dissipation graph.

Note 3: Mirror gain is the current gain of the current mirror which is used as the non-inverting input.

∆Mirror Gain is the % change in AIfor two different mirror currents at any given temperature.

Note 4: See Supply Rejection graphs.

Typical Performance Characteristics

Open Loop Gain Open Loop Gain

00778839 00778840

Note: Shaded area refers to LM359

Open Loop Gain Gain Bandwidth Product

00778841 00778842

LM359

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Typical Performance Characteristics (Continued)

Slew Rate

Gain and Phase

Feedback Gain=−100

00778843 00778844

Inverting Input Bias Current Inverting Input Bias Current

00778845 00778846

Note: Shaded area refers to LM359

Mirror Gain Mirror Gain

00778847 00778848

Note: Shaded area refers to LM359

LM359

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Typical Performance Characteristics (Continued)

Mirror Gain Mirror Current

00778849 00778850

Note: Shaded area refers to LM359

Supply Current Supply Rejection

00778851 00778852

Supply Rejection Output Sink Current

00778853 00778854

LM359

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Typical Performance Characteristics (Continued)

Output Swing Output Impedance

00778855 00778856

Amplifier to Amplifier

Coupling (Input Referred) Noise Voltage

00778857 00778858

Maximum Power Dissipation

00778859

Note: Shaded area refers to LM359J/LM359N

Application Hints

The LM359 consists of two wide bandwidth, decompensated

current differencing (Norton) amplifiers. Although similar in

operation to the original LM3900, design emphasis for these

amplifiers has been placed on obtaining much higher fre-

quency performance as illustrated in Figure 1.

This significant improvement in frequency response is the

result of using a common-emitter/common-base (cascode)

gain stage which is typical in many discrete and integrated

video and RF circuit designs. Another versatile aspect of

these amplifiers is the ability to externally program many

internal amplifier parameters to suit the requirements of a

wide variety of applications in which this type of amplifier can

be used.

LM359

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Application Hints (Continued)

DC BIASING

The LM359 is intended for single supply voltage operation

which requires DC biasing of the output. The current mirror

circuitry which provides the non-inverting input for the ampli-

fier also facilitates DC biasing the output. The basic opera-

tion of this current mirror is that the current (both DC and AC)

flowing into the non-inverting input will force an equal

amount of current to flow into the inverting input . The mirror

gain (A

) specification is the measure of how closely these

two currents match. For more details see National Applica-

tion Note AN-72.

DC biasing of the output is accomplished by establishing a

reference DC current into the (+) input, I

(+), and requiring

the output to provide the (−) input current. This forces the

output DC level to be whatever value necessary (within the

output voltage swing of the amplifier) to provide this DC

reference current, Figure 2.

The DC input voltage at each input is a transistor V

(.0.6 V

) and must be considered for DC biasing. For

most applications, the supply voltage, V

, is suitable and

convenient for establishing I

(+). The inverting input bias

current, I

(−), is a direct function of the programmable input

stage current (see current programmability section) and to

obtain predictable output DC biasing set I

(+) ≥10I

(−).

00778806

FIGURE 1.

00778807

FIGURE 2.

LM359

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Application Hints (Continued)

The following figures illustrate typical biasing schemes for

AC amplifiers using the LM359:

The nV

biasing configuration is most useful for low noise

applications where a reduced input impedance can be ac-

commodated (see typical applications section).

OPERATING CURRENT PROGRAMMABILITY (I

SET

)

The input bias current, slew rate, gain bandwidth product,

output drive capability and total device power consumption

of both amplifiers can be simultaneously controlled and op-

timized via the two programming pins I

SET(OUT)

and I

SET(IN)

SET(OUT)

The output set current (I

SET(OUT)

) is equal to the amount of

current sourced from pin 1 and establishes the class A

biasing current for the Darlington emitter follower output

stage. Using a single resistor from pin 1 to ground, as shown

in Figure 6, this current is equal to:

The output set current can be adjusted to optimize the

amount of current the output of the amplifier can sink to drive

load capacitance and for loads connected to V

.The maxi-

mum output sinking current is approximately 10 times

SET(OUT)

. This set current is best used to reduce the total

device supply current if the amplifiers are not required to

drive small load impedances.

SET(IN)

00778808

FIGURE 3. Biasing an Inverting AC Amplifier

00778809

FIGURE 4. Biasing a Non-Inverting AC Amplifier

00778810

FIGURE 5. nV

Biasing

00778811

FIGURE 6. Establishing the Output Set Current

LM359

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Application Hints (Continued)

The input set current I

SET(IN)

is equal to the current flowing

into pin 8. A resistor from pin 8 to V

sets this current to be:

SET(IN)

is most significant in controlling the AC characteris-

tics of the LM359 as it directly sets the total input stage

current of the amplifiers which determines the maximum

slew rate, the frequency of the open loop dominant pole, the

input resistance of the (−) input and the biasing current I

(−).

All of these parameters are significant in wide band amplifier

design. The input stage current is approximately 3 times

SET(IN)

and by using this relationship the following first order

approximations for these AC parameters are:

where C

comp

is the total capacitance from the compensation

pin (pin 3 or pin 13) to ground, A

VOL

is the low frequency

open loop voltage gain in V/V and an ambient temperature of

25˚C is assumed (KT/q = 26 mV and β

typ

= 150). I

SET(IN)

also

controls the DC input bias current by the expression:

which is important for DC biasing considerations.

The total device supply current (for both amplifiers) is also a

direct function of the set currents and can be approximated

by:

supply

.27xI

SET(OUT)

+11xI

SET(IN)

with each set current programmed by individual resistors.

PROGRAMMING WITH A SINGLE RESISTOR

Operating current programming may also be accomplished

using only one resistor by letting I

SET(IN)

equal I

SET(OUT)

. The

programming current is now referred to as I

SET

and it is

created by connecting a resistor from pin 1 to pin 8 (Figure

8).

This configuration does not affect any of the internal set

current dependent parameters differently than previously

discussed except the total supply current which is now equal

to:

supply

.37xI

SET

Care must be taken when using resistors to program the set

current to prevent significantly increasing the supply voltage

above the value used to determine the set current. This

would cause an increase in total supply current due to the

resulting increase in set current and the maximum device

power dissipation could be exceeded. The set resistor val-

ue(s) should be adjusted for the new supply voltage.

One method to avoid this is to use an adjustable current

source which has voltage compliance to generate the set

current as shown in Figure 9.

This circuit allows I

SET

to remain constant over the entire

supply voltage range of the LM359 which also improves

power supply ripple rejection as illustrated in the Typical

Performance Characteristics. It should be noted, however,

that the current through the LM334 as shown will change

linearly with temperature but this can be compensated for

(see LM334 data sheet).

00778812

FIGURE 7. Establishing the Input Set Current

00778813

ISET(IN) =I

SET(OUT) =I

SET

FIGURE 8. Single Resistor Programming of I

SET

00778814

FIGURE 9. Current Source Programming of I

SET

LM359

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Application Hints (Continued)

Pin 1 must never be shorted to ground or pin 8 never shorted

to V

without limiting the current to 2 mA or less to prevent

catastrophic device failure.

CONSIDERATIONS FOR HIGH FREQUENCY

OPERATION

The LM359 is intended for use in relatively high frequency

applications and many factors external to the amplifier itself

must be considered. Minimization of stray capacitances and

their effect on circuit operation are the primary requirements.

The following list contains some general guidelines to help

accomplish this end:

1. Keep the leads of all external components as short as

possible.

2. Place components conducting signal current from the

output of an amplifier away from that amplifier’s non-

inverting input.

3. Use reasonably low value resistances for gain setting

and biasing.

4. Use of a ground plane is helpful in providing a shielding

effect between the inputs and from input to output. Avoid

using vector boards.

5. Use a single-point ground and single-point supply distri-

bution to minimize crosstalk. Always connect the two

grounds (one from each amplifier) together.

6. Avoid use of long wires (>2") but if necessary, use

shielded wire.

7. Bypass the supply close to the device with a low induc-

tance, low value capacitor (typically a 0.01 µF ceramic)

to create a good high frequency ground. If long supply

leads are unavoidable, a small resistor (∼10Ω) in series

with the bypass capacitor may be needed and using

shielded wire for the supply leads is also recommended.

COMPENSATION

The LM359 is internally compensated for stability with closed

loop inverting gains of 10 or more. For an inverting gain of

less than 10 and all non-inverting amplifiers (the amplifier

always has 100% negative current feedback regardless of

the gain in the non-inverting configuration) some external

frequency compensation is required because the stray ca-

pacitance to ground from the (−) input and the feedback

resistor add additional lagging phase within the feedback

loop. The value of the input capacitance will typically be in

the range of 6 pF to 10 pF for a reasonably constructed

circuit board. When using a feedback resistance of 30 kΩor

less, the best method of compensation, without sacrificing

slew rate, is to add a lead capacitor in parallel with the

feedback resistor with a value on the order of 1 pF to 5 pF as

shown in Figure 10 .

Another method of compensation is to increase the effective

value of the internal compensation capacitor by adding ca-

pacitance from the COMP pin of an amplifier to ground. An

external 20 pF capacitor will generally compensate for all

gain settings but will also reduce the gain bandwidth product

and the slew rate. These same results can also be obtained

by reducing I

SET(IN)

if the full capabilities of the amplifier are

not required. This method is termed over-compensation.

Another area of concern from a stability standpoint is that of

capacitive loading. The amplifier will generally drive capaci-

tive loads up to 100 pF without oscillation problems. Any

larger C loads can be isolated from the output as shown in

Figure 11. Over-compensation of the amplifier can also be

used if the corresponding reduction of the GBW product can

be afforded.

In most applications using the LM359, the input signal will be

AC coupled so as not to affect the DC biasing of the ampli-

fier. This gives rise to another subtlety of high frequency

circuits which is the effective series inductance (ESL) of the

coupling capacitor which creates an increase in the imped-

ance of the capacitor at high frequencies and can cause an

unexpected gain reduction. Low ESL capacitors like solid

tantalum for large values of C and ceramic for smaller values

are recommended. A parallel combination of the two types is

even better for gain accuracy over a wide frequency range.

00778815

Cf= 1 pF to 5 pF for stability

FIGURE 10. Best Method of Compensation

00778816

FIGURE 11. Isolating Large Capacitive Loads

LM359

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Application Hints (Continued)

AMPLIFIER DESIGN EXAMPLES

The ability of the LM359 to provide gain at frequencies

higher than most monolithic amplifiers can provide makes it

most useful as a basic broadband amplification stage. The

design of standard inverting and non-inverting amplifiers,

though different than standard op amp design due to the

current differencing inputs, also entail subtle design differ-

ences between the two types of amplifiers. These differ-

ences will be best illustrated by design examples. For these

examples a practical video amplifier with a passband of 8 Hz

to 10 MHz and a gain of 20 dB will be used. It will be

assumed that the input will come from a 75Ωsource and

proper signal termination will be considered. The supply

voltage is 12 V

and single resistor programming of the

operating current, I

SET

, will be used for simplicity.

AN INVERTING VIDEO AMPLIFIER

1. Basic circuit configuration:

00778817

2. Determine the required I

SET

from the characteristic

curves for gain bandwidth product.

GBW

MIN

=10x10MHz=100MHz

For a flat response to 10 MHz a closed loop response to

two octaves above 10 MHz (40 MHz) will be sufficient.

Actual GBW = 10 x 40 MHz = 400 MHz

SET

required = 0.5 mA

3. Determine maximum value for R

to provide stable DC

biasing

Optimum output DC level for maximum symmetrical

swing without clipping is:

f(MAX)

can now be found:

This value should not be exceeded for predictable DC

biasing.

4. Select R

to be large enough so as not to appreciably

load the input termination resistance:

≥750Ω; Let R

= 750Ω

5. Select R

for appropriate gain:

7.5 kΩis less than the calculated R

f(MAX)

so DC predict-

ability is insured.

6. Since R

= 7.5k, for the output to be biased to 5.1 V

the reference current I

(+) must be:

Now R

can be found by:

7. Select C

to provide the proper gain for the 8 Hz mini-

mum input frequency:

A larger value of C

will allow a flat frequency response

down to 8 Hz and a 0.01 µF ceramic capacitor in parallel

with C

will maintain high frequency gain accuracy.

8. Test for peaking of the frequency response and add a

feedback “lead” capacitor to compensate if necessary.

LM359

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Application Hints (Continued)

Final Circuit Using Standard 5%

Tolerance Resistor Values:

00778818

Circuit Performance:

00778819

Vo(DC) = 5.1V

Differential phase error <1˚ for 3.58 MHz fIN

Differential gain error <0.5% for 3.58 MHz fIN

f−3 dB low = 2.5 Hz

A NON-INVERTING VIDEO AMPLIFIER

For this case several design considerations must be dealt

with.

•The output voltage (AC and DC) is strictly a function of

the size of the feedback resistor and the sum of AC and

DC “mirror current” flowing into the (+) input.

•The amplifier always has 100% current feedback so ex-

ternal compensation is required. Add a small (1 pF–5 pF)

feedback capacitance to leave the amplifier’s open loop

response and slew rate unaffected.

•To prevent saturating the mirror stage the total AC and

DC current flowing into the amplifier’s (+) input should be

less than 2 mA.

•The output’s maximum negative swing is one diode

above ground due to the V

diode clamp at the (−) input.

LM359

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Application Hints (Continued)

DESIGN EXAMPLE

= 50 mV (MAX), f

= 10 MHz (MAX), desired circuit

BW = 20 MHz, A

= 20 dB, driving source impedance = 75Ω,

= 12V.

1. Basic circuit configuration:

00778820

2. Select I

SET

to provide adequate amplifier bandwidth so

that the closed loop bandwidth will be determined by R

and C

. To do this, the set current should program an

amplifier open loop gain of at least 20 dB at the desired

closed loop bandwidth of the circuit. For this example,

an I

SET

of 0.5 mA will provide 26 dB of open loop gain at

20 MHz which will be sufficient. Using single resistor

programming for I

SET

3. Since the closed loop bandwidth will be determined by

to obtain a 20 MHz bandwidth, both R

and C

should be

kept small. It can be assumed that C

can be in the range

of 1 pF to 5 pF for carefully constructed circuit boards to

insure stability and allow a flat frequency response. This

will limit the value of R

to be within the range of:

Also, for a closed loop gain of +10, R

must be 10 times

where r

is the mirror diode resistance.

4. So as not to appreciably load the 75Ωinput termination

resistance the value of (R

) is set to 750Ω.

5. For A

= 10; R

is set to 7.5 kΩ.

6. The optimum output DC level for symmetrical AC swing

is:

7. The DC feedback current must be:

DC biasing predictability will be insured because 640 µA

is greater than the minimum of I

SET

/5 or 100 µA.

For gain accuracy the total AC and DC mirror current

should be less than 2 mA. For this example the maxi-

mum AC mirror current will be:

therefore the total mirror current range will be 574 µA to

706 µA which will insure gain accuracy.

8. R

can now be found:

9. Since R

will be 750Ωand r

is fixed by the DC

mirror current to be:

must be 750Ω–40Ωor 710Ωwhich can be a 680Ω

resistor in series with a 30Ωresistor which are standard

5% tolerance resistor values.

10. As a final design step, C

must be selected to pass the

lower passband frequency corner of 8 Hz for this ex-

ample.

A larger value may be used and a 0.01 µF ceramic

capacitor in parallel with C

will maintain high frequency

gain accuracy.

LM359

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Application Hints (Continued)

Final Circuit Using Standard 5% Tolerance Resistor Values

00778821

Circuit Performance

00778822

Vo(DC) = 5.4V

Differential phase error <0.5˚

Differential gain error <2%

f−3 dB low = 2.5 Hz

LM359

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Application Hints (Continued)

GENERAL PRECAUTIONS

The LM359 is designed primarily for single supply operation

but split supplies may be used if the negative supply voltage

is well regulated as the amplifiers have no negative supply

rejection.

The total device power dissipation must always be kept in

mind when selecting an operating supply voltage, the pro-

gramming current, I

SET

, and the load resistance, particularly

when DC coupling the output to a succeeding stage. To

prevent damaging the current mirror input diode, the mirror

current should always be limited to 10 mA, or less, which is

important if the input is susceptible to high voltage tran-

sients. The voltage at any of the inputs must not be forced

more negative than −0.7V without limiting the current to 10

mA.

The supply voltage must never be reversed to the device;

however, plugging the device into a socket backwards would

then connect the positive supply voltage to the pin that has

no internal connection (pin 5) which may prevent inadvertent

device failure.

Typical Applications

DC Coupled Inputs

Inverting

00778823

Non-Inverting

00778824

•Eliminates the need for an input coupling capacitor

•Input DC level must be stable and can exceed the supply voltage of the LM359 provided that maximum input currents are not

exceeded.

LM359

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Typical Applications (Continued)

Noise Reduction using nV

Biasing

00778825

Biasing with a Negative Supply

00778826

•R1 and C2 provide additional filtering of the negative

biasing supply

Typical Input Referred Noise Performance

00778827

Adding a JFET Input Stage

00778828

•FET input voltage mode op amp

•For A

= +1; BW = 40 MHz, S

= 60 V/µs; C

=51pF

•For A

= +11; BW = 24 MHz, S

= 130 V/µs; C

=5pF

•For A

= +100; BW = 4.5 MHz, S

= 150 V/µs; C

=2pF

•V

is typically <25 mV; 100Ωpotentiometer allows a

adjust range of ≈±200 mV

•Inputs must be DC biased for single supply operation

LM359

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Typical Applications (Continued)

Photo Diode Amplifier

00778829

D1 ∼RCA N-Type Silicon P-I-N Photodiode

•Frequency response of greater than 10 MHz

•If slow rise and fall times can be tolerated the gate on the output can be removed. In this case the rise and the fall time of the

LM359 is 40 ns.

•T

PDL

= 45 ns, T

PDH

=50ns−T

L output

LM359

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Typical Applications (Continued)

Balanced Line Driver

00778830

•1 MHz−3 dB bandwidth with gain of 10 and 0 dbm into 600Ω

•0.3% distortion at full bandwidth; reduced to 0.05% with bandwidth of 10 kHz

•Will drive C

= 1500 pF with no additional compensation, ±0.01 µF with C

comp

= 180 pF

•70 dB signal to noise ratio at 0 dbm into 600Ω, 10 kHz bandwidth

LM359

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Typical Applications (Continued)

Difference Amplifier

00778831

•CMRR is adjusted for max at expected CM input signal

•Wide bandwidth

•70 dB CMRR typ

•Wide CM input voltage range

Voltage Controlled Oscillator

00778832

•5 MHz operation

•T

L output

LM359

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Typical Applications (Continued)

Phase Locked Loop

00778833

•Up to 5 MHz operation

•T

L compatible input

All diodes = 1N914

LM359

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Typical Applications (Continued)

Squarewave Generator

00778834

f=1MHz

Output is TTL compatible

Frequency is adjusted by R1&C(R1!R2)

Pulse Generator

00778836

Output is TTL compatible

Duty cycle is adjusted by R1

Frequency is adjusted by C

f=1MHz

Duty cycle = 20%

LM359

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Typical Applications (Continued)

Crystal Controlled Sinewave Oscillator

00778837

Vo= 500 mVp-p

f = 9.1 MHz

THD <2.5%

High Performance 2 Amplifier Biquad Filter(s)

00778835

•The high speed of the LM359 allows the center frequency Q

product of the filter to be: f

≤5 MHz

•The above filter(s) maintain performance over wide temperature range

•One half of LM359 acts as a true non-inverting integrator so only 2 amplifiers (instead of 3 or 4) are needed for the biquad

filter structure

LM359

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Typical Applications (Continued)

DC Biasing Equations for V

01(DC)

02(DC)

Type I

Type II

Type III

Analysis and Design Equations

Type V

(notch) H

o(LP)

o(BP)

o(HP)

o(BR)

IBPLPOR

∞R

/R — R/R

——

II HP BP C

∞∞ R

/R — — R

/RC C

/C —

III Notch/

—C

∞R

———

Triangle Waveform Generator

00778838

V2 output is TTL compatible

R2 adjusts for symmetry of the triangle waveform

Frequency is adjusted with R5 and C

LM359

www.national.com23

Schematic Diagram

00778803

LM359

www.national.com 24

Physical Dimensions inches (millimeters)

unless otherwise noted

S.O. Package (M)

Order Number LM359M or LM359MX

NS Package Number M14A

Molded Dual-In-Line Package (N)

Order Number LM359N

NS Package Number N14A

LM359

www.national.com25

Notes

LIFE SUPPORT POLICY

NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT

DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL

COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:

1. Life support devices or systems are devices or

systems which, (a) are intended for surgical implant

into the body, or (b) support or sustain life, and

whose failure to perform when properly used in

accordance with instructions for use provided in the

labeling, can be reasonably expected to result in a

significant injury to the user.

2. A critical component is any component of a life

support device or system whose failure to perform

can be reasonably expected to cause the failure of

the life support device or system, or to affect its

safety or effectiveness.

BANNED SUBSTANCE COMPLIANCE

National Semiconductor certifies that the products and packing materials meet the provisions of the Customer Products

Stewardship Specification (CSP-9-111C2) and the Banned Substances and Materials of Interest Specification

(CSP-9-111S2) and contain no ‘‘Banned Substances’’ as defined in CSP-9-111S2.

National Semiconductor

Americas Customer

Support Center

Email: new.feedback@nsc.com

Tel: 1-800-272-9959

National Semiconductor

Europe Customer Support Center

Fax: +49 (0) 180-530 85 86

Email: europe.support@nsc.com

Deutsch Tel: +49 (0) 69 9508 6208

English Tel: +44 (0) 870 24 0 2171

Français Tel: +33 (0) 1 41 91 8790

National Semiconductor

Asia Pacific Customer

Support Center

Email: ap.support@nsc.com

National Semiconductor

Japan Customer Support Center

Fax: 81-3-5639-7507

Email: jpn.feedback@nsc.com

Tel: 81-3-5639-7560

www.national.com

LM359 Dual, High Speed, Programmable, Current Mode (Norton) Amplifiers

National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.

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