ADUC843BSZ62-3 - Analog Devices

MicroConverter

12-Bit ADCs and DACs with

Embedded High Speed 62-kB Flash MCU

ADuC841/ADuC842/ADuC843

Rev. 0

Information furnished by Analog Devices is believed to be accurate and reliable.

However, no responsibility is assumed by Analog Devices for its use, nor for any

infringements of patents or other rights of third parties that may result from its use.

Specifications subject to change without notice. No license is granted by implication

or otherwise under any patent or patent rights of Analog Devices. Trademarks and

registered trademarks are the property of their respective owners.

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.

Tel: 781.329.4700 www.analog.com

FEATURES

Pin compatable ugrade of ADuC812/ADuC831/ADuC832

Increased performance

Single-cycle 20 MIPS 8052 core

High speed 420 kSPS 12-bit ADC

Increased memory

Up to 62 kBytes on-chip Flash/EE program memory

4 kBytes on-chip Flash/EE data memory

In-circuit reprogrammable

Flash/EE, 100 year retention, 100 kCycle endurance

2304 bytes on-chip data RAM

Smaller package

8 mm × 8 mm chip scale package

52-lead PQFP—pin compatable upgrade

Analog I/O

8-channel, 420 kSPS high accuracy, 12-bit ADC

On-chip, 15 ppm/°C voltage reference

DMA controller, high speed ADC-to-RAM capture

Two 12-bit voltage output DACs1

Dual output PWM ∑-∆ DACs

On-chip temperature monitor function

8052 based core

8051 compatible instruction set (20 MHz max)

High performance single-cycle core

32 kHz external crystal, on-chip programmable PLL

12 interrupt sources, 2 priority levels

Dual data pointers, extended 11-bit stack pointer

On-chip peripherals

Time interval counter (TIC)

UART, I2C®, and SPI® Serial I/O

Watchdog timer (WDT)

Power supply monitor (PSM)

Power

Normal: 4.5 mA @ 3 V (core CLK = 2.098 MHz)

Power-down: 10 µA @ 3 V2

Development tools

Low cost, comprehensive development system

incorporating nonintrusive single-pin emulation,

IDE based assembly and C source debugging

APPLICATIONS

Optical networking—laser power control

Base station systems

Precision instrumentation, smart sensors

Transient capture systems

DAS and communications systems

1 ADuC841/ADuC842 only.

2 ADuC842/ADuC843 only, ADuC841 driven directly by external crystal.

FUNCTIONAL BLOCK DIAGRAM

62 kBYTES FLASH/EE PROGRAM MEMORY

4 kBYTES FLASH/EE DATA MEMORY

2304 BYTES USER RAM

3×16 BIT TIMERS

1×REAL TIME CLOCK

4× PARALLEL

PORTS

20 MIPS 8052 BASED MCU WITH ADDITIONAL

PERIPHERALS

ADuC841/ADuC842/ADuC843

XTAL2XTAL1

TEMP

SENSOR

CREF

INTERNAL

BAND GAP

VREF

ADC0

ADC1

ADC5

ADC6

ADC7

OSC

12-BIT

DAC DAC

PWM0

T/H

MUX

12-BIT ADC

HARDWARE

CALIBRATON

BUF

DAC

BUF

PWM1

12-BIT

DAC

16-BIT

Σ-∆DAC

16-BIT

PWM

16-BIT

PWM

POWER SUPPLY MON

WATCHDOG TIMER

UART, I

C, AND SPI

SERIAL I/O

MUX

16-BIT

Σ-∆DAC

03260-0-001

PLL

Figure 1.

GENERAL DESCRIPTION

The ADuC841/ADuC842/ADuC843 are complete smart

transducer front ends, that integrates a high performance self-

calibrating multichannel ADC, a dual DAC, and an optimized

single-cycle 20 MHz 8-bit MCU (8051 instruction set

compatible) on a single chip.

The ADuC841 and ADuC842 are identical with the exception of

the clock oscillator circuit; the ADuC841 is clocked directly

from an external crystal up to 20 MHz whereas the ADuC842

uses a 32 kHz crystal with an on-chip PLL generating a

programmable core clock up to 16.78 MHz.

The ADuC843 is identical to the ADuC842 except that the

ADuC843 has no analog DAC outputs.

The microcontroller is an optimized 8052 core offering up to

20 MIPS peak performance. Three different memory options

are available offering up to 62 kBytes of nonvolatile Flash/EE

program memory. Four kBytes of nonvolatile Flash/EE data

memory, 256 bytes RAM, and 2 kBytes of extended RAM are

also integrated on-chip.

(continued on page 15)

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 2 of 88

TABLE OF CONTENTS

Specifications..................................................................................... 3

Absolute Maximum Ratings............................................................ 8

ESD Caution.................................................................................. 8

Pin Configurations and Functional Descriptions ........................ 9

Terminology .................................................................................... 11

ADC Specifications .................................................................... 11

DAC Specifications..................................................................... 11

Typical Performance Characteristics ........................................... 12

Functional Description .................................................................. 16

8052 Instruction Set ................................................................... 16

Other Single-Cycle Core Features ............................................ 18

Memory Organization ............................................................... 19

Special Function Registers (SFRs)............................................ 20

Accumulator SFR (ACC)........................................................... 21

Special Function Register Banks .............................................. 22

ADC Circuit Information.......................................................... 23

Calibrating the ADC .................................................................. 30

Nonvolatile Flash/EE Memory ................................................. 31

Using Flash/EE Data Memory .................................................. 34

User Interface to On-Chip Peripherals.................................... 38

On-Chip PLL............................................................................... 41

Pulse-Width Modulator (PWM).............................................. 42

Serial Peripheral Interface (SPI)............................................... 45

I2C Compatible Interface........................................................... 48

Dual Data Pointer....................................................................... 51

Power Supply Monitor............................................................... 52

Watchdog Timer......................................................................... 53

Time Interval Counter (TIC).................................................... 54

8052 Compatible On-Chip Peripherals................................... 57

Timer/Counter 0 and 1 Operating Modes.............................. 62

Timer/Counter Operating Modes............................................ 64

UART Serial Interface................................................................ 65

SBUF ............................................................................................ 65

Interrupt System ......................................................................... 70

Hardware Design Considerations............................................ 72

Other Hardware Considerations.............................................. 76

Development Tools .................................................................... 77

QuickStart Development System ............................................. 77

Timing Specifications, , .................................................................. 78

Outline Dimensions....................................................................... 86

Ordering Guides......................................................................... 87

REVISION HISTORY

Revision 0: Initial Version

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 3 of 88

SPECIFICATIONS1

Table 1. AVDD = DVDD = 2.7 V to 3.6 V or 4.75 V to 5.25 V; VREF = 2.5 V internal reference, fCORE = 16.78 MHz @ 5 V 8.38 MHz @ 3 V;

all specifications TA = TMIN to TMAX, unless otherwise noted

Parameter VDD = 5 V VDD = 3 V Unit Test Conditions/Comments

ADC CHANNEL SPECIFICATIONS

DC ACCURACY2, 3 fSAMPLE = 120 kHz, see the Typical

Performance Characteristics for typical

performance at other values of fSAMPLE

Resolution 12 12 Bits

Integral Nonlinearity ±1 ±1 LSB max 2.5 V internal reference

±0.3 ±0.3 LSB typ

Differential Nonlinearity +1/–0.9 +1/–0.9 LSB max 2.5 V internal reference

±0.3 ±0.3 LSB typ

Integral Nonlinearity4 ±2 ±1.5 LSB max 1 V external reference

Differential Nonlinearity4 +1.5/–0.9 +1.5/–0.9 LSB max 1 V external reference

Code Distribution 1 1 LSB typ ADC input is a dc voltage

CALIBRATED ENDPOINT ERRORS5, 6

Offset Error ±3 ±2 LSB max

Offset Error Match ±1 ±1 LSB typ

Gain Error ±3 ±2 LSB max

Gain Error Match ±1 ±1 LSB typ

DYNAMIC PERFORMANCE fIN = 10 kHz sine wave

SAMPLE = 120 kHz

Signal-to-Noise Ratio (SNR)7 71 71 dB typ

Total Harmonic Distortion (THD) –85 –85 dB typ

Peak Harmonic or Spurious Noise –85 –85 dB typ

Channel-to-Channel Crosstalk8 –80 –80 dB typ

ANALOG INPUT

Input Voltage Range 0 to VREF 0 to VREF V

Leakage Current ±1 ±1 µA max

Input Capacitance 32 32 pF typ

TEMPERATURE SENSOR9

Voltage Output at 25°C 700 700 mV typ

Voltage TC –1.4 –1.4 mV/°C typ

Accuracy ±1.5 ±1.5 °C typ Internal/External 2.5 V VREF

DAC CHANNEL SPECIFICATIONS DAC load to AGND

Internal Buffer Enabled

ADuC841/ADuC842 Only

L = 10 kΩ, CL = 100 pF

DC ACCURACY10

Resolution 12 12 Bits

Relative Accuracy ±3 ±3 LSB typ

Differential Nonlinearity11 –1 –1 LSB max Guaranteed 12-bit monotonic

±1/2 ±1/2 LSB typ

Offset Error ±50 ±50 mV max VREF range

Gain Error ±1 ±1 % max AVDD range

±1 ±1 % typ VREF range

Gain Error Mismatch 0.5 0.5 % typ % of full-scale on DAC1

ANALOG OUTPUTS

Voltage Range_0 0 to VREF 0 to VREF V typ DAC VREF = 2.5 V

Voltage Range_1 0 to VDD 0 to VDD V typ DAC VREF = VDD

Output Impedance 0.5 0.5 Ω typ

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 4 of 88

Parameter VDD = 5 V VDD = 3 V Unit Test Conditions/Comments

DAC AC CHARACTERISTICS

Voltage Output Settling Time 15 15 µs typ

Full-scale settling time to within

½ LSB of final value

Digital-to-Analog Glitch Energy 10 10 nV-sec typ 1 LSB change at major carry

DAC CHANNEL SPECIFICATIONS12, 13

Internal Buffer Disabled ADuC841/ADuC842 Only

DC ACCURACY10

Resolution 12 12 Bits

Relative Accuracy ±3 ±3 LSB typ

Differential Nonlinearity11 –1 –1 LSB max Guaranteed 12-bit monotonic

±1/2 ±1/2 LSB typ

Offset Error ±5 ±5 mV max VREF range

Gain Error ±0.5 ±0.5 % typ VREF range

Gain Error Mismatch4 0.5 0.5 % typ % of full-scale on DAC1

ANALOG OUTPUTS

Voltage Range_0 0 to VREF 0 to VREF V typ DAC VREF = 2.5 V

REFERENCE INPUT/OUTPUT REFERENCE OUTPUT14

Output Voltage (VREF) 2.5 2.5 V

Accuracy ±10 ±10 mV Max

Of VREF measured at the CREF pin

TA = 25°C

Power Supply Rejection 65 67 dB typ

Reference Temperature Coefficient ±15 ±15 ppm/°C typ

Internal VREF Power-On Time 2 2 ms typ

EXTERNAL REFERENCE INPUT15

Voltage Range (VREF) 4 1 1 V min

DD V

DD V max

Input Impedance 20 20 kΩ typ

Input Leakage 1 1 µA max

Internal band gap deselected via

ADCCON1.6

POWER SUPPLY MONITOR (PSM)

DVDD Trip Point Selection Range

2.93

3.08

V min

V max

Two trip points selectable in this

range programmed via TPD1–0 in

PSMCON, 3 V part only

DVDD Power Supply Trip Point Accuracy ±2.5 % max

WATCHDOG TIMER (WDT) 4

Timeout Period 0

2000

ms min

ms max

Nine timeout periods selectable in

this range

FLASH/EE MEMORY RELIABILITY CHARACTERISTICS16

Endurance17 100,000 100,000 Cycles min

Data Retention18 100 100 Years min

DIGITAL INPUTS

Input Leakage Current (Port 0, EA) ±10 ±10 µA max VIN = 0 V or VDD

±1 ±1 µA typ VIN = 0 V or VDD

Logic 1 Input Current

(All Digital Inputs), SDATA, SCLOCK ±10 ±10 µA max VIN = VDD

±1 ±1 µA typ VIN = VDD

Logic 0 Input Current (Ports 1, 2, 3) SDATA, SCLOCK –75 –25 µA max

–40 –15 µA typ VIL = 450 mV

Logic 1 to Logic 0 Transition Current (Ports 2 and 3) –660 –250 µA max VIL = 2 V

RESET

–400

±10

105

–140

±10

µA typ

µA max

µA min

µA max

VIL = 2 V

VIN = 0 V

VIN = 5 V, 3 V Internal Pull Down

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 5 of 88

Parameter VDD = 5 V VDD = 3 V Unit Test Conditions/Comments

LOGIC INPUTS4

INPUT VOLTAGES

All Inputs Except SCLOCK, SDATA, RESET, and

XTAL1

VINL, Input Low Voltage

VINH, Input High Voltage

SDATA

VINL, Input Low Voltage

VINH, Input High Voltage

0.8

2.0

0.8

2.0

0.4

2.0

0.8

2.0

V max

V min

V max

V min

SCLOCK and RESET Only4

(Schmitt-Triggered Inputs)

VT+

VT–

VT+ – VT–

1.3

3.0

0.8

1.4

0.3

0.85

0.95

0.25

0.4

1.1

0.3

0.85

V min

V max

V min

V max

V min

V max

CRYSTAL OSCILLATOR

Logic Inputs, XTAL1 Only

VINL, Input Low Voltage 0.8 0.4 V typ

VINH, Input High Voltage 3.5 2.5 V typ

XTAL1 Input Capacitance 18 18 pF typ

XTAL2 Output Capacitance 18 18 pF typ

MCU CLOCK RATE 16.78

8.38

MHz max

ADuC842/ADuC843 Only

ADuC841 Only

DIGITAL OUTPUTS

Output High Voltage (VOH) 2.4 V min VDD = 4.5 V to 5.5 V

4 V typ ISOURCE = 80 µA

2.4 V min VDD = 2.7 V to 3.3 V

2.6 V typ ISOURCE = 20 µA

Output Low Voltage (VOL)

ALE, Ports 0 and 2 0.4 0.4 V max ISINK = 1.6 mA

0.2 0.2 V typ ISINK = 1.6 mA

Port 3 0.4 0.4 V max ISINK = 4 mA

SCLOCK/SDATA 0.4 0.4 V max ISINK = 8 mA, I2C Enabled

Floating State Leakage Current4 ±10 ±10 µA max

±1 ±1 µA typ

STARTUP TIME At any core CLK

At Power-On 500 500 ms typ

From Idle Mode 100 100 µs typ

From Power-Down Mode

Wake-up with INT0 Interrupt 150 400 µs typ

Wake-up with SPI/I2C Interrupt 150 400 µs typ

Wake-up with External RESET 150 400 µs typ

After External RESET in Normal Mode 30 30 ms typ

After WDT Reset in Normal Mode 3 3 ms typ Controlled via WDCON SFR

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 6 of 88

Parameter VDD = 5 V VDD = 3 V Unit Test Conditions/Comments

POWER REQUIREMENTS19, 20

Power Supply Voltages

AVDD/DVDD – AGND 2.7 V min AVDD/DVDD = 3 V nom

3.6 V max

4.75 V min AVDD/DVDD = 5 V nom

5.25 V max

Power Supply Currents Normal Mode21

DVDD Current4 10 4.5 mA typ Core CLK = 2.097 MHz

AVDD Current 1.7 1.7 mA max Core CLK = 2.097 MHz

DVDD Current 38 12 mA max Core CLK = 16.78MHz/8.38 MHz 5 V/3 V

33 10 mA typ Core CLK = 16.78MHz/8.38 MHz 5 V/3 V

AVDD Current 1.7 1.7 mA max Core CLK = 16.78MHz/8.38 MHz 5 V/3 V

DVDD Current4

Power Supply Currents Idle Mode21

45 N/A mA max

Core CLK = 20MHz ADuC841 Only

DVDD Current 4.5 2.2 mA typ Core CLK = 2.097 MHz

AVDD Current 3 2 µA typ Core CLK = 2.097 MHz

DVDD Current4 12 5 mA max Core CLK = 16.78MHz/8.38 MHz 5 V/3 V

10 3.5 mA typ Core CLK = 16.78MHz/8.38 MHz 5 V/3 V

AVDD Current 3 2 µA typ Core CLK = 16.78MHz/8.38 MHz 5 V/3 V

Power Supply Currents Power-Down Mode21 Core CLK = any frequency

DVDD Current 28

µA max

µA typ

Oscillator Off / TIMECON.1 = 0

AVDD Current 2 1 µA typ Core CLK = any frequency

ADuC841 Only

DVDD Current4 3 1 mA max TIMECON.1 = 1

DVDD Current4 50

µA max

µA typ

Core CLK = any frequency

ADuC842/ADuC843 Only

Oscillator On

Typical Additional Power Supply Currents

PSM Peripheral 15 10 µA typ AVDD = DVDD

ADC4 1.0

2.8

1.0

1.8

mA min

mA max

MCLK Divider = 32

MCLK Divider = 2

DAC 150 130 µA typ

See footnotes on the next page.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 7 of 88

1 Temperature Range –40°C to +85°C.

2 ADC linearity is guaranteed during normal MicroConverter core operation.

3 ADC LSB size = VREF/212, i.e., for internal VREF = 2.5 V, 1 LSB = 610 µV, and for external VREF = 1 V, 1 LSB = 244 µV.

4 These numbers are not production tested but are supported by design and/or characterization data on production release.

5 Offset and gain error and offset and gain error match are measured after factory calibration.

6 Based on external ADC system components, the user may need to execute a system calibration to remove additional external channel errors to achieve these

specifications.

7 SNR calculation includes distortion and noise components.

8 Channel-to-channel crosstalk is measured on adjacent channels.

9 The temperature monitor gives a measure of the die temperature directly; air temperature can be inferred from this result.

10 DAC linearity is calculated using:

Reduced code range of 100 to 4095, 0 V to VREF range.

Reduced code range of 100 to 3945, 0 V to VDD range.

DAC output load = 10 kΩ and 100 pF.

11 DAC differential nonlinearity specified on 0 V to VREF and 0 V to VDD ranges.

12 DAC specification for output impedance in the unbuffered case depends on DAC code.

13 DAC specifications for ISINK, voltage output settling time, and digital-to-analog glitch energy depend on external buffer implementation in unbuffered mode. DAC in

unbuffered mode tested with OP270 external buffer, which has a low input leakage current.

14 Measured with CREF pin decoupled with 0.47 µF capacitor to ground. Power-up time for the internal reference is determined by the value of the decoupling capacitor

chosen for the CREF pin.

15 When using an external reference device, the internal band gap reference input can be bypassed by setting the ADCCON1.6 bit.

16 Flash/EE memory reliability characteristics apply to both the Flash/EE program memory and the Flash/EE data memory.

17 Endurance is qualified to 100,000 cycles as per JEDEC Std. 22 method A117 and measured at –40°C, +25°C, and +85°C. Typical endurance at 25°C is 700,000 cycles.

18 Retention lifetime equivalent at junction temperature (TJ) = 55°C as per JEDEC Std. 22 method A117. Retention lifetime based on an activation energy of 0.6 eV derates

with junction temperature as shown in Figure 38 in the Flash/EE Memory Reliability section.

19 Power supply current consumption is measured in normal, idle, and power-down modes under the following conditions:

Normal Mode: Reset = 0.4 V, digital I/O pins = open circuit, Core Clk changed via CD bits in PLLCON (ADuC842/ADuC843), core executing internal

software loop.

Idle Mode: Reset = 0.4 V, digital I/O pins = open circuit, Core Clk changed via CD bits in PLLCON (ADuC842/ADuC843), PCON.0 = 1, core execution

suspended in idle mode.

Power-Down Mode: Reset = 0.4 V, all Port 0 pins = 0.4 V, All other digital I/O and Port 1 pins are open circuit, Core Clk changed via CD bits in PLLCON

(ADuC842/ADuC843), PCON.0 = 1, core execution suspended in power-down mode, OSC turned on or off via OSC_PD bit (PLLCON.7) in

PLLCON SFR (ADuC842/ADuC843).

20 DVDD power supply current increases typically by 3 mA (3 V operation) and 10 mA (5 V operation) during a Flash/EE memory program or erase cycle.

21 Power supply currents are production tested at 5.25 V and 3.3 V for a 5 V and 3 V part, respectively.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 8 of 88

ABSOLUTE MAXIMUM RATINGS

Table 2. TA = 25°C, unless otherwise noted

Parameter Rating

AVDD to DVDD –0.3 V to +0.3 V

AGND to DGND –0.3 V to +0.3 V

DVDD to DGND, AVDD to AGND –0.3 V to +7 V

Digital Input Voltage to DGND –0.3 V to DVDD + 0.3 V

Digital Output Voltage to DGND –0.3 V to DVDD + 0.3 V

VREF to AGND –0.3 V to AVDD + 0.3 V

Analog Inputs to AGND –0.3 V to AVDD + 0.3 V

Operating Temperature Range,

Industrial

ADuC841BS,ADuC842BS,ADuC843BS

ADuC841BCP, ADuC842BCP,

ADuC843BCP

–40°C to +85°C

Storage Temperature Range –65°C to +150°C

Junction Temperature 150°C

θJA Thermal Impedance (ADuC84xBS) 90°C/W

θJA Thermal Impedance (ADuC84xBCP) 52°C/W

Lead Temperature, Soldering

Vapor Phase (60 sec)

Infrared (15 sec)

215°C

220°C

Stresses above those listed under Absolute Maximum Ratings

may cause permanent damage to the device. This is a stress

rating only and functional operation of the device at these or

any other conditions above those indicated in the operational

section of this specification is not implied. Exposure to absolute

maximum rating conditions for extended periods may affect

device reliability.

ESD CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the

human body and test equipment and can discharge without detection. Although this product features

proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy

electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance

degradation or loss of functionality.

WATCHDOG

TIMER

256 BYTES USER

RAM

POWER SUPPLY

MONITOR

TEMP

SENSOR

BAND GAP

REFERENCE

AGND

DGND

RESET

POR

SDATA\MOSI

MISO

XTAL1

ADuC841/ADuC842/ADuC843

ADC

CONTROL

AND

CALIBRATION

DAC1

DAC

CONTROL

12-BIT

VOLTAGE

OUTPUT DAC

T2EX

INT0

INT1

PSEN

ALE

SINGLE-PIN

EMULATOR

TxD

RxD

4 kBYTES DATA

FLASH/EE

62 kBYTES PROGRAM

FLASH/EE INCLUDING

USER DOWNLOAD

MODE

ASYNCHRONOUS

SERIAL PORT

(UART)

8052

MCU

CORE

DOWNLOADER

DEBUGGER

SYNCHRONOUS

SERIAL INTERFACE

C AND SPI )

16-BIT

COUNTER

TIMERS

TIME INTERVAL

COUNTER

(WAKE-UP CCT)

XTAL2

OSC

2 kBYTES USER XRAM

2× DATA POINTERS

11-BIT STACK POINTER

12-BIT

VOLTAGE

OUTPUT DAC

MUX

...

12-BIT

ADC

DC0

DC1

DC6

DC7

DAC0

MUX

16-BIT

Σ-∆DAC

PWM0

PWM1

16-BIT

PWM

16-BIT

PWM

CONTROL

16-BIT

Σ-∆DAC

T/H

REF

BUF

UART

TIMER

SCLOCK

03260-0-002

PLL

Figure 2. ADuC Block Diagram (Shaded Areas are Features Not Present on the ADuC812),

No DACs on ADuC843, PLL on ADuC842/ADuC843 Only.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 9 of 88

PIN CONFIGURATIONS AND FUNCTIONAL DESCRIPTIONS

52 51 50 49 48 43 42 41 4047 46 45 44

14 15 16 17 18 19 20 21 22 23 24 25 26

PIN 1

IDENTIFIER

TOP VIEW

(Not to Scale)

P0.7/AD

P0.6/AD

P0.5/AD

P0.4/AD

DGND

P0.3/AD

P0.2/AD

P0.1/AD1

P0.0/AD

ALE

PSEN

P1.7/ADC7

RESET

P3.0/RXD

P3.1/TXD

P3.2/INT0

P3.3/INT1/MISO/PWM1

P3.4/T0/PWMC/PWM0/EXTCLK*

P3.5/T1/CONVST

P3.6/WR

P3.7/RD

SCLOCK

P1.0/ADC0/T2

P1.1/ADC1/T2EX

P1.2/ADC2

P1.3/ADC3

AGND

REF

DAC0

DAC1

P1.4/ADC4

P1.5/ADC5/SS

P1.6/ADC6

P2.7/PWM1/A15/A23

P2.6/PWM0/A14/A22

P2.5/A13/A21

P2.4/A12/A20

DGND

XTAL2

XTAL1

P2.3/A11/A19

P2.2/A10/A18

P2.1/A9/A17

P2.0/A8/A16

SDATA/MOSI

DGND

03260-0-003

ADuC841/ADuC842/ADuC843

52-LEAD PQFP

*EXTCLK NOT PRESENT ON THE ADuC841

Figure 3. 52-Lead PQPF

P1.1/ADC1/T2EX

P1.2/ADC2

P1.3/ADC3

AGND

REF

DAC0

DAC1

P1.4/ADC4

P1.5/ADC5/SS

P1.6/ADC6

P.7/ADC7

RESET

P3.0/RxD

P3.1/TxD

P3.2/INT0

P3.3/INT1/MISO/PWM1

DGND

P3.4/T0/PWMC/PWM0/EXTCLK*

P3.5/T1/CONVST

P3.6/WR

P3.7/RD

SCLOCK

P2.7/A15/A23

P2.6/A14/A22

P2.5/A13/A21

P2.4/A12/A20

DGND

XTAL1

P2.3/A11/A19

P2.2/A10/A18

P2.1/A9/A17

P2.0/A8/A16

SDATA/MOSI

P1.0/ADC0/T2

P0.7/AD7

P0.6/AD6

P0.5/AD5

P0.4/AD4

DGND

P0.3/AD3

P0.2/AD2

P0.1/AD1

P0.0/AD0

ALE

PSEN

PIN 1

IDENTIFIER

XTAL2

TOP VIEW

(Not to Scale)

03260-0-004

ADuC841/ADuC842/ADuC843

56-LEAD CSP

*EXTCLK NOT PRESENT ON THE ADuC841

Figure 4. 56-Lead CSP

Table 3. Pin Function Descriptions

Mnemonic Type Function

DVDD P Digital Positive Supply Voltage. 3 V or 5 V nominal.

AVDD P Analog Positive Supply Voltage. 3 V or 5 V nominal.

CREF I/O Decoupling Input for On-Chip Reference. Connect a 0.47 µF capacitor between this pin and AGND.

VREF NC Not connected. This was reference out on the ADuC812; the CREF pin should be used instead.

AGND G Analog Ground. Ground reference point for the analog circuitry.

P1.0–P1.7 I Port 1 is an 8-bit input port only. Unlike other ports, Port 1 defaults to analog input mode. To configure any of

these port pins as a digital input, write a 0 to the port bit.

ADC0–ADC7 I Analog Inputs. Eight single-ended analog inputs. Channel selection is via ADCCON2 SFR.

T2 I

Timer 2 Digital Input. Input to Timer/Counter 2. When enabled, Counter 2 is incremented in response to a 1-to-0

transition of the T2 input.

T2EX I Digital Input. Capture/reload trigger for Counter 2; also functions as an up/down control input for Counter 2.

SS I Slave Select Input for the SPI Interface.

SDATA I/O User Selectable, I2C Compatible, or SPI Data Input/Output Pin.

SCLOCK I/O Serial Clock Pin for I2C Compatible or for SPI Serial Interface Clock.

MOSI I/O SPI Master Output/Slave Input Data I/O Pin for SPI Interface.

MISO I/O SPI Master Input/Slave Output Data I/O Pin for SPI Serial Interface.

DAC0 O Voltage Output from DAC0. This pin is a no connect on the ADuC843.

DAC1 O Voltage Output from DAC1. This pin is a no connect on the ADuC843.

RESET I Digital Input. A high level on this pin for 24 master clock cycles while the oscillator is running resets the device.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 10 of 88

Mnemonic Type Function

P3.0–P3.7 I/O Port 3 is a bidirectional port with internal pull-up resistors. Port 3 pins that have 1s written to them are pulled high

by the internal pull-up resistors, and in that state can be used as inputs. As inputs, Port 3 pins being pulled

externally low source current because of the internal pull-up resistors. Port 3 pins also contain various secondary

functions, which are described below.

PWMC I PWM Clock Input.

PWM0 O PWM0 Voltage Output. PWM outputs can be configured to use Ports 2.6 and 2.7 or Ports 3.4 and 3.3.

PWM1 O PWM1 Voltage Output. See the CFG841/CFG842 register for further information.

RxD I/O Receiver Data Input (Asynchronous) or Data Input/Output (Synchronous) of the Serial (UART) Port.

TxD O Transmitter Data Output (Asynchronous) or Clock Output (Synchronous) of the Serial (UART) Port.

INT0 I Interrupt 0. Programmable edge or level triggered interrupt input; can be programmed to one of two priority

levels. This pin can also be used as a gate control input to Timer 0.

INT1 I Interrupt 1. Programmable edge or level triggered interrupt input; can be programmed to one of two priority

levels. This pin can also be used as a gate control input to Timer 1.

T0 I Timer/Counter 0 Input.

T1 I Timer/Counter 1 Input.

CONVST I Active Low Convert Start Logic Input for the ADC Block when the External Convert Start Function is Enabled. A

low-to-high transition on this input puts the track-and-hold into hold mode and starts the conversion.

EXTCLK I Input for External Clock Signal. Has to be enabled via the CFG842 register.

WR O Write Control Signal, Logic Output. Latches the data byte from Port 0 into the external data memory.

RD O Read Control Signal, Logic Output. Enables the external data memory to Port 0.

XTAL2 O Output of the Inverting Oscillator Amplifier.

XTAL1 I Input to the Inverting Oscillator Amplifier.

DGND G Digital Ground. Ground reference point for the digital circuitry.

P2.0–P2.7

(A8–A15)

(A16–A23)

I/O Port 2 is a bidirectional port with internal pull-up resistors. Port 2 pins that have 1s written to them are pulled high

by the internal pull-up resistors, and in that state can be used as inputs. As inputs, Port 2 pins being pulled

externally low source current because of the internal pull-up resistors. Port 2 emits the middle and high-order

address bytes during accesses to the external 24-bit external data memory space.

PSEN O Program Store Enable, Logic Output. This pin remains low during internal program execution. PSEN is used to

enable serial download mode when pulled low through a resistor on power-up or reset. On reset this pin will

momentarily become an input and the status of the pin is sampled. If there is no pulldown resistor in place the pin

will go momentarilly high and then user code will execute. If a pull-down resistor is in place, the embedded serial

download/debug kernel will execute.

ALE O

Address Latch Enable, Logic Output. This output is used to latch the low byte and page byte for 24-bit address

space accesses of the address into external data memory.

EA I External Access Enable, Logic Input. When held high, this input enables the device to fetch code from internal

program memory locations. The parts do not support external code memory. This pin should not be left floating.

P0.7–P0.0

(A0-A7)

I/O Port 0 is an 8-bit open-drain bidirectional I/O port. Port 0 pins that have 1s written to them float, and in that state

can be used as high impedance inputs. Port 0 is also the multiplexed low-order address and data bus during

accesses to external data memory. In this application, it uses strong internal pull-ups when emitting 1s.

Types: P = Power, G = Ground, I= Input, O = Output., NC = No Connect

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 11 of 88

TERMINOLOGY

ADC SPECIFICATIONS

Integral Nonlinearity

The maximum deviation of any code from a straight line

passing through the endpoints of the ADC transfer function.

The endpoints of the transfer function are zero scale, a point

½ LSB below the first code transition, and full scale, a point

½ LSB above the last code transition.

Differential Nonlinearity

The difference between the measured and the ideal 1 LSB

change between any two adjacent codes in the ADC.

Offset Error

The deviation of the first code transition (0000 . . . 000) to

(0000 . . . 001) from the ideal, i.e., +½ LSB.

Gain Error

The deviation of the last code transition from the ideal AIN

voltage (Full Scale – ½ LSB) after the offset error has been

adjusted out.

Signal-to-(Noise + Distortion) Ratio

The measured ratio of signal to (noise + distortion) at the

output of the ADC. The signal is the rms amplitude of the

fundamental. Noise is the rms sum of all nonfundamental

signals up to half the sampling frequency (fS/2), excluding dc.

The ratio depends on the number of quantization levels in the

digitization process; the more levels, the smaller the quantization

noise. The theoretical signal-to-(noise + distortion) ratio for an

ideal N-bit converter with a sine wave input is given by

Signal-to-(Noise + Distortion) = (6.02N + 1.76) dB

Thus for a 12-bit converter, this is 74 dB.

Total Harmonic Distortion (THD)

The ratio of the rms sum of the harmonics to the fundamental.

DAC SPECIFICATIONS

Relative Accuracy

Relative accuracy or endpoint linearity is a measure of the

maximum deviation from a straight line passing through the

endpoints of the DAC transfer function. It is measured after

adjusting for zero error and full-scale error.

Voltage Output Settling Time

The amount of time it takes for the output to settle to a

specified level for a full-scale input change.

Digital-to-Analog Glitch Impulse

The amount of charge injected into the analog output when the

inputs change state. It is specified as the area of the glitch in nV-sec.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 12 of 88

TYPICAL PERFORMANCE CHARACTERISTICS

The typical performance plots presented in this section

illustrate typical performance of the ADuC841/ADuC842/

ADuC843 under various operating conditions.

Figure 5 and Figure 6 show typical ADC integral nonlinearity

(INL) errors from ADC Code 0 to Code 4095 at 5 V and 3 V

supplies, respectively. The ADC is using its internal reference

(2.5 V) and is operating at a sampling rate of 152 kHz; the

typical worst-case errors in both plots are just less than 0.3 LSB.

Figure 7 and Figure 8 also show ADC INL at a higher sampling

rate of 400 kHz. Figure 9 and Figure 10 show the variation in

worst-case positive (WCP) INL and worst-case negative (WCN)

INL versus external reference input voltage.

Figure 11 and Figure 12 show typical ADC differential

nonlinearity (DNL) errors from ADC Code 0 to Code 4095 at

5 V and 3 V supplies, respectively. The ADC is using its internal

reference (2.5 V) and is operating at a sampling rate of 152 kHz;

the typical worst-case errors in both plots are just less than

0.2 LSB. Figure 13 and Figure 14 show the variation in worst-

case positive (WCP) DNL and worst-case negative (WCN) DNL

versus external reference input voltage.

Figure 15 shows a histogram plot of 10,000 ADC conversion

results on a dc input with VDD = 5 V. The plot illustrates an

excellent code distribution pointing to the low noise

performance of the on-chip precision ADC.

Figure 16 shows a histogram plot of 10,000 ADC conversion

results on a dc input for VDD = 3 V. The plot again illustrates a

very tight code distribution of 1 LSB with the majority of codes

appearing in one output pin.

Figure 17 and Figure 18 show typical FFT plots for the parts.

These plots were generated using an external clock input. The

ADC is using its internal reference (2.5 V), sampling a full-scale,

10 kHz sine wave test tone input at a sampling rate of 149.79 kHz.

The resulting FFTs shown at 5 V and 3 V supplies illustrate an

excellent 100 dB noise floor, 71 dB signal-to-noise ratio (SNR),

and THD greater than –80 dB.

Figure 19 and Figure 20 show typical dynamic performance

versus external reference voltages. Again, excellent ac perform-

ance can be observed in both plots with some roll-off being

observed as VREF falls below 1 V.

Figure 21 shows typical dynamic performance versus sampling

frequency. SNR levels of 71 dB are obtained across the sampling

range of the parts.

Figure 22 shows the voltage output of the on-chip temperature

sensor versus temperature. Although the initial voltage output at

25°C can vary from part to part, the resulting slope of −1. 4 mV/°C

is constant across all parts.

ADC CODES

–1.00 511

LSBs

1023 2047 2559 3071

–0.8

1535 3583

–0.6

–0.4

–0.2

0.2

0.4

0.6

0.8

1.0

/ DV

= 5V

= 152kHz

4095

03260-0-005

Figure 5. Typical INL Error, VDD = 5 V, fs = 152 kHz

ADC CODES

1.0

511 1023 1535 2047 2559

LSBs

0.6

0.2

–0.2

–0.6

–1.0

0.8

0.4

–0.4

–0.8

3071 35830 4095

/DV

= 3V

= 152kHz

03260-0-006

Figure 6. Typical INL Error, VDD = 3 V, fs = 152 kHz

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 13 of 88

ADC CODES

–1.0 0 511

LSBs

1023 2047 2559 3071

–0.8

1535 3583

–0.6

–0.4

–0.2

0.2

0.4

0.6

0.8

1.0

/DV

= 5V

= 400kHz

CD = 4

4095

03260-0-098

Figure 7. Typical INL Error, VDD = 5 V, fS = 400 kHz

ADC CODES

–1.0 0 511

LSBs

1023 2047 2559 3071

–0.8

1535 3583

–0.6

–0.4

–0.2

0.2

0.4

0.6

0.8

1.0

/DV

= 3V

= 400kHz

CD = 4

4095

03260-0-099

Figure 8. Typical INL Error, VDD = 3 V, fS = 400 kHz

EXTERNAL REFERENCE (V)

1.2

WCP–INL (LSBs)

0.8

0.4

–0.4

–0.6

1.0

0.6

0.2

–0.2

AVDD/DVDD = 5V

= 152kHz

0.5 1.0 1.5 2.0 2.5 5.0

0.6

0.4

–0.4

–0.6

0.2

–0.2

WCN–INL (LSBs)

WCN INL

WCP INL

03260-0-007

Figure 9. Typical Worst-Case INL Error vs. VREF, VDD = 5 V

EXTERNAL REFERENCE (V)

WCP–INL

(LSBs)

0.8

0.4

–0.4

–0.8

0.6

0.2

–0.2

/DV

= 3V

= 152kHz

0.5 1.5 2.5

WCN–INL

(LSBs)

–0.6

0.8

0.4

–0.4

–0.8

0.6

0.2

–0.2

–0.6

3.02.01.0

WCN INL

WCP INL

03260-0-008

Figure 10. Typical Worst-Case INL Error vs. VREF, VDD = 3 V

ADC CODES

1.0

511 1023 1535 2047 2559

LSBs

0.6

0.2

–0.2

–0.6

–1.0

0.8

0.4

–0.4

–0.8

3071 35830 4095

/DV

= 5V

= 152kHz

03260-0-009

Figure 11. Typical DNL Error, VDD = 5 V

ADC CODES

1.0

511 1023 1535 2047 2559

LSBs

0.6

0.2

–0.2

–0.6

–1.0

0.8

0.4

–0.4

–0.8

3071 35830 4095

/DV

= 3V

= 152kHz

03260-0-010

Figure 12. Typical DNL Error, VDD = 3 V

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 14 of 88

EXTERNAL REFERENCE (V)

–0.6 0.5

WCP–DNL

(LSBs)

1.0 2.0 2.5 5.0

–0.4

1.5

–0.2

0.2

0.4

0.6

WCN–DNL

(LSBs)

–0.4

–0.6

–0.2

0.2

0.4

0.6

/DV

= 5V

= 152kHz

WCP DNL

WCN DNL

03260-0-011

Figure 13. Typical Worst-Case DNL Error vs. VREF, VDD = 5 V

EXTERNAL REFERENCE (V)

WCP–DNL (LSBs)

0.7

0.5

0.1

–0.5

–0.7

0.3

–0.3

/DV

= 3V

S = 152kHz

0.5 1.0 1.5 2.0 2.5 3.0

WCN–DNL (LSBs)

WCP DNL

WCN DNL

–0.1

0.7

0.5

0.1

–0.5

–0.7

0.3

–0.3

–0.1

03260-0-012

Figure 14. Typical Worst-Case DNL Error vs. VREF, VDD = 3 V

CODE

817 818 819 820 821

10000

OCCURRENCE

8000

6000

4000

2000

03260-0-013

Figure 15. Code Histogram Plot, VDD = 5 V

CODE

10000

817 818 819 820 821

OCCURRENCE

8000

6000

4000

2000

9000

7000

5000

3000

1000

03260-0-014

Figure 16. Code Histogram Plot, VDD = 3 V

–20

–40

–60

–80

–100

–120

–140

–160

dBs

20 FREQUENCY (kHz)

1007060504030

/DV

= 5V

= 152kHz

= 9.910kHz

SNR = 71.3dB

THD = –88.0dB

ENOB = 11.6

03260-0-015

Figure 17. Dynamic Performance at VDD = 5 V

–20

–40

–60

–80

–100

–120

–140

–160

dBs

20 FREQUENCY (kHz)

1007060504030

/DV

= 3V

= 149.79kHz

= 9.910kHz

SNR = 71.0dB

THD = –83.0dB

ENOB = 11.5

03260-0-016

Figure 18. Dynamic Performance at VDD = 3 V

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 15 of 88

EXTERNAL REFERENCE (V)

50 0.5

SNR (dBs)

1.0 2.0 2.5 5.0

1.5

THD (dBs)

–100

–95

–90

–85

–80

–75

–70

/DV

= 5V

= 152kHz

SNR

THD

03260-0-017

Figure 19. Typical Dynamic Performance vs. VREF, VDD = 5 V

EXTERNAL REFERENCE (V)

SNR (dBs)

/DV

= 3V

= 152kHz

0.5 1.5 2.5

THD (dBs)

SNR

THD

–70

–75

–85

–100

–80

–95

–90

1.0 2.0 3.0

03260-0-018

Figure 20. Typical Dynamic Performance vs. VREF, VDD = 3 V

FREQUENCY (kHz)

92.262

SNR

(dBs)

119.050

172.620

199.410

226.190

145.830

65.476

03260-0-019

300.000

350.000

400.000

AVDD /DVDD = 5V

Figure 21. Typical Dynamic Performance vs. Sampling Frequency

TEMPERATURE (

03260-0-100

0.2

0.3

0.4

0.5

0.6

0.7

0.8

0.9

–40 25 85

VOLTAGE

/DV

= 3V

SLOPE = –1.4mV/

Figure 22. Typical Temperature Sensor Output vs. Temperature

GENERAL DESCRIPTION (continued)

The parts also incorporate additional analog functionality with

two 12-bit DACs, power supply monitor, and a band gap

reference. On-chip digital peripherals include two 16-bit ∑-∆.

DACs, a dual output 16-bit PWM, a watchdog timer, a time

interval counter, three timers/counters, and three serial I/O

ports (SPI, I2C, and UART).

On the ADuC812 and the ADuC832, the I2C and SPI interfaces

share some of the same pins. For backwards compatibility, this

is also the case for the ADuC841/ADuC842/ADuC843.

However, there is also the option to allow SPI operate separately

on P3.3, P3.4, and P3.5, while I2C uses the standard pins. The

I2C interface has also been enhanced to offer repeated start,

general call, and quad addressing.

On-chip factory firmware supports in-circuit serial download

and debug modes (via UART) as well as single-pin emulation

mode via the EA pin. A functional block diagram of the parts is

shown on the first page.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 16 of 88

FUNCTIONAL DESCRIPTION

8052 INSTRUCTION SET

Table 4 documents the number of clock cycles required for each

instruction. Most instructions are executed in one or two clock

cycles, resulting in a 16 MIPS peak performance when operating

at PLLCON = 00H on the ADuC842/ADuC843. On the ADuC841,

20 MIPS peak performance is possible with a 20 MHz external

crystal.

Table 4. Instructions

Mnemonic Description Bytes Cycles

Arithmetic

ADD A,Rn Add register to A 1 1

ADD A,@Ri Add indirect memory to A 1 2

ADD A,dir Add direct byte to A 2 2

ADD A,#data Add immediate to A 2 2

ADDC A,Rn Add register to A with carry 1 1

ADDC A,@Ri Add indirect memory to A with carry 1 2

ADDC A,dir Add direct byte to A with carry 2 2

ADD A,#data Add immediate to A with carry 2 2

SUBB A,Rn Subtract register from A with borrow 1 1

SUBB A,@Ri Subtract indirect memory from A with borrow 1 2

SUBB A,dir Subtract direct from A with borrow 2 2

SUBB A,#data Subtract immediate from A with borrow 2 2

INC A Increment A 1 1

INC Rn Increment register 1 1

INC @Ri Increment indirect memory 1 2

INC dir Increment direct byte 2 2

INC DPTR Increment data pointer 1 3

DEC A Decrement A 1 1

DEC Rn Decrement register 1 1

DEC @Ri Decrement indirect memory 1 2

DEC dir Decrement direct byte 2 2

MUL AB Multiply A by B 1 9

DIV AB Divide A by B 1 9

DA A Decimal adjust A 1 2

Logic

ANL A,Rn AND register to A 1 1

ANL A,@Ri AND indirect memory to A 1 2

ANL A,dir AND direct byte to A 2 2

ANL A,#data AND immediate to A 2 2

ANL dir,A AND A to direct byte 2 2

ANL dir,#data AND immediate data to direct byte 3 3

ORL A,Rn OR register to A 1 1

ORL A,@Ri OR indirect memory to A 1 2

ORL A,dir OR direct byte to A 2 2

ORL A,#data OR immediate to A 2 2

ORL dir,A OR A to direct byte 2 2

ORL dir,#data OR immediate data to direct byte 3 3

XRL A,Rn Exclusive-OR register to A 1 1

XRL A,@Ri Exclusive-OR indirect memory to A 2 2

XRL A,#data Exclusive-OR immediate to A 2 2

XRL dir,A Exclusive-OR A to direct byte 2 2

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 17 of 88

Mnemonic Description Bytes Cycles

XRL A,dir Exclusive-OR indirect memory to A 2 2

XRL dir,#data Exclusive-OR immediate data to direct 3 3

CLR A Clear A 1 1

CPL A Complement A 1 1

SWAP A Swap nibbles of A 1 1

RL A Rotate A left 1 1

RLC A Rotate A left through carry 1 1

RR A Rotate A right 1 1

RRC A Rotate A right through carry 1 1

Data Transfer

MOV A,Rn Move register to A 1 1

MOV A,@Ri Move indirect memory to A 1 2

MOV Rn,A Move A to register 1 1

MOV @Ri,A Move A to indirect memory 1 2

MOV A,dir Move direct byte to A 2 2

MOV A,#data Move immediate to A 2 2

MOV Rn,#data Move register to immediate 2 2

MOV dir,A Move A to direct byte 2 2

MOV Rn, dir Move register to direct byte 2 2

MOV dir, Rn Move direct to register 2 2

MOV @Ri,#data

MOV dir,@Ri

MOV @Ri,dir

Move immediate to indirect memory

Move indirect to direct memory

Move direct to indirect memory

MOV dir,dir Move direct byte to direct byte 3 3

MOV dir,#data Move immediate to direct byte 3 3

MOV DPTR,#data Move immediate to data pointer 3 3

MOVC A,@A+DPTR Move code byte relative DPTR to A 1 4

MOVC A,@A+PC Move code byte relative PC to A 1 4

MOVX A,@Ri Move external (A8) data to A 1 4

MOVX A,@DPTR Move external (A16) data to A 1 4

MOVX @Ri,A Move A to external data (A8) 1 4

MOVX @DPTR,A Move A to external data (A16) 1 4

PUSH dir Push direct byte onto stack 2 2

POP dir Pop direct byte from stack 2 2

XCH A,Rn Exchange A and register 1 1

XCH A,@Ri Exchange A and indirect memory 1 2

XCHD A,@Ri Exchange A and indirect memory nibble 1 2

XCH A,dir Exchange A and direct byte 2 2

Boolean

CLR C Clear carry 1 1

CLR bit Clear direct bit 2 2

SETB C Set carry 1 1

SETB bit Set direct bit 2 2

CPL C Complement carry 1 1

CPL bit Complement direct bit 2 2

ANL C,bit AND direct bit and carry 2 2

ANL C,/bit AND direct bit inverse to carry 2 2

ORL C,bit OR direct bit and carry 2 2

ORL C,/bit OR direct bit inverse to carry 2 2

MOV C,bit Move direct bit to carry 2 2

MOV bit,C Move carry to direct bit 2 2

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 18 of 88

Mnemonic Description Bytes Cycles

Branching

JMP @A+DPTR Jump indirect relative to DPTR 1 3

RET Return from subroutine 1 4

RETI Return from interrupt 1 4

ACALL addr11 Absolute jump to subroutine 2 3

AJMP addr11 Absolute jump unconditional 2 3

SJMP rel Short jump (relative address) 2 3

JC rel Jump on carry equal to 1 2 3

JNC rel Jump on carry equal to 0 2 3

JZ rel Jump on accumulator = 0 2 3

JNZ rel Jump on accumulator not equal to 0 2 3

DJNZ Rn,rel Decrement register, JNZ relative 2 3

LJMP Long jump unconditional 3 4

LCALL addr16 Long jump to subroutine 3 4

JB bit,rel Jump on direct bit = 1 3 4

JNB bit,rel Jump on direct bit = 0 3 4

JBC bit,rel Jump on direct bit = 1 and clear 3 4

CJNE A,dir,rel Compare A, direct JNE relative 3 4

CJNE A,#data,rel Compare A, immediate JNE relative 3 4

CJNE Rn,#data,rel Compare register, immediate JNE relative 3 4

CJNE @Ri,#data,rel Compare indirect, immediate JNE relative 3 4

DJNZ dir,rel Decrement direct byte, JNZ relative 3 4

Miscellaneous

NOP No operation 1 1

1. One cycle is one clock.

2. Cycles of MOVX instructions are four cycles when they have 0 wait state. Cycles of MOVX instructions are 4 + n cycles when they have n wait states.

3. Cycles of LCALL instruction are three cycles when the LCALL instruction comes from interrupt.

OTHER SINGLE-CYCLE CORE FEATURES

Timer Operation

Timers on a standard 8052 increment by 1 with each machine

cycle. On the ADuC841/ADuC842/ADuC843, one machine

cycle is equal to one clock cycle; therefore the timers increment

at the same rate as the core clock.

ALE

The output on the ALE pin on a standard 8052 part is a clock at

1/6th of the core operating frequency. On the ADuC841/

ADuC842/ADuC843 the ALE pin operates as follows. For a

single machine cycle instruction,ALE is high for the first half of

the machine cycle and low for the second half. The ALE output

is at the core operating frequency. For a two or more machine

cycle instruction, ALE is high for the first half of the first

machine cycle and low for the rest of the machine cycles.

External Memory Access

There is no support for external program memory access on the

parts. When accessing external RAM, the EWAIT register may

need to be programmed to give extra machine cycles to MOVX

commands. This is to account for differing external RAM access

speeds.

EWAIT SFR

SFR Address 9FH

Power-On Default 00H

Bit Addressable No

This special function register (SFR) is programmed with the

number of wait states for a MOVX instruction. This value can

range from 0H to 7H.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 19 of 88

MEMORY ORGANIZATION

The ADuC841/ADuC842/ADuC843 each contain four different

memory blocks:

• Up to 62 kBytes of on-chip Flash/EE program memory

• 4 kBytes of on-chip Flash/EE data memory

• 256 bytes of general-purpose RAM

• 2 kBytes of internal XRAM

Flash/EE Program Memory

The parts provide up to 62 kBytes of Flash/EE program mem-

ory to run user code. The user can run code from this internal

memory only. Unlike the ADuC812, where code execution can

overflow from the internal code space to external code space

once the PC becomes greater than 1FFFH, the parts do not

support the roll-over from F7FFH in internal code space to

F800H in external code space. Instead, the 2048 bytes between

F800H and FFFFH appear as NOP instructions to user code.

This internal code space can be downloaded via the UART

serial port while the device is in-circuit. 56 kBytes of the

program memory can be reprogrammed during run time; thus

the code space can be upgraded in the field by using a user

defined protocol, or it can be used as a data memory. This is

discussed in more detail in the Flash/EE Memory section.

For the 32 kBytes memory model, the top 8 kBytes function as

the ULOAD space; this is explained in the Flash/EE Memory

section.

Flash/EE Data Memory

4 kBytes of Flash/EE data memory are available to the user and

can be accessed indirectly via a group of control registers

mapped into the special function register (SFR) area. Access to

the Flash/EE data memory is discussed in detail in the Flash/EE

Memory section.

General-Purpose RAM

The general-purpose RAM is divided into two separate

memories: the upper and the lower 128 bytes of RAM. The

lower 128 bytes of RAM can be accessed through direct or

indirect addressing. The upper 128 bytes of RAM can be

accessed only through indirect addressing because it shares the

same address space as the SFR space, which can be accessed

only through direct addressing.

The lower 128 bytes of internal data memory are mapped as

shown in Figure 23. The lowest 32 bytes are grouped into four

banks of eight registers addressed as R0 to R7. The next 16 bytes

(128 bits), locations 20H to 2FH above the register banks, form

a block of directly addressable bit locations at Bit Addresses

00H to 7FH. The stack can be located anywhere in the internal

memory address space, and the stack depth can be expanded up

to 2048 bytes.

Reset initializes the stack pointer to location 07H and incre-

ments it once before loading the stack to start from location

08H, which is also the first register (R0) of register bank 1. Thus,

if the user needs to use more than one register bank, the stack

pointer should be initialized to an area of RAM not used for

data storage.

00 07H

0FH

17H

1FH

2FH

7FH

00H

08H

10H

18H

20H

RESET VALUE OF

STACK POINTER

30H

FOUR BANKS OF EIGHT

REGISTERS

R0 TO R7

BIT-ADDRESSABLE

(BIT ADDRESSES)

GENERAL-PURPOSE

AREA

BANKS

SELECTED

VIA

BITS IN PSW

03260-0-021

Figure 23. Lower 128 Bytes of Internal Data Memory

The parts contain 2048 bytes of internal XRAM, 1792 bytes of

which can be configured to an extended 11-bit stack pointer.

By default, the stack operates exactly like an 8052 in that it rolls

over from FFH to 00H in the general-purpose RAM. On the

parts, however, it is possible (by setting CFG841.7 or CFG842.7)

to enable the 11-bit extended stack pointer. In this case, the

stack rolls over from FFH in RAM to 0100H in XRAM.

The 11-bit stack pointer is visible in the SP and SPH SFRs. The

SP SFR is located at 81H as with a standard 8052. The SPH SFR

is located at B7H. The 3 LSBs of this SFR contain the 3 extra bits

necessary to extend the 8-bit stack pointer into an 11-bit stack

pointer.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 20 of 88

UPPER 1792

BYTES OF

ON-CHIP XRAM

(DATA + STACK

FOR EXSP = 1,

DATA ONLY

FOR EXSP = 0)

256 BYTES OF

ON-CHIP DATA

RAM

(DATA +

STACK)

LOWER 256

BYTES OF

ON-CHIP XRAM

(DATA ONLY)

00H

FFH

00H

07FFH

CFG841.7 = 0

CFG842.7 = 0

100H

03260-0-022

CFG841.7 = 1

CFG842.7 = 1

Figure 24. Extended Stack Pointer Operation

External Data Memory (External XRAM)

Just like a standard 8051 compatible core, the ADuC841/

ADuC842/ADuC843 can access external data memory by using

a MOVX instruction. The MOVX instruction automatically

outputs the various control strobes required to access the data

memory.

The parts, however, can access up to 16 MBytes of external data

memory. This is an enhancement of the 64 kBytes of external

data memory space available on a standard 8051 compatible core.

The external data memory is discussed in more detail in the

Hardware Design Considerations section.

Internal XRAM

The parts contain 2 kBytes of on-chip data memory. This

memory, although on-chip, is also accessed via the MOVX

instruction. The 2 kBytes of internal XRAM are mapped into

the bottom 2 kBytes of the external address space if the

CFG841/CFG842 bit is set. Otherwise, access to the external

data memory occurs just like a standard 8051. When using the

internal XRAM, Ports 0 and 2 are free to be used as general-

purpose I/O.

EXTERNAL

DATA

MEMORY

SPACE

(24-BIT

ADDRESS

SPACE)

000000H

FFFFFFH

CFG841.0 = 0

CFG842.0 = 0

EXTERNAL

DATA

MEMORY

SPACE

(24-BIT

ADDRESS

SPACE)

000000H

FFFFFFH

CFG841.0 = 1

CFG842.0 = 0

0007FFH

000800H

2 kBYTES

ON-CHIP

XRAM

03260-0-023

Figure 25. Internal and External XRAM

SPECIAL FUNCTION REGISTERS (SFRS)

The SFR space is mapped into the upper 128 bytes of internal

data memory space and is accessed by direct addressing only. It

provides an interface between the CPU and all on-chip periph-

erals. A block diagram showing the programming model of the

parts via the SFR area is shown in Figure 26.

All registers, except the program counter (PC) and the four

general-purpose register banks, reside in the SFR area. The SFR

registers include control, configuration, and data registers, which

provide an interface between the CPU and all on-chip peripherals.

128-BYTE

SPECIAL

FUNCTION

AREA

62-kBYTE

ELECTRICALLY

REPROGRAMMABLE

NONVOLATILE

FLASH/EE PROGRAM

MEMORY

8051

COMPATIBLE

CORE OTHER ON-CHIP

PERIPHERALS

TEMPERATURE

SENSOR

2×12-BIT DACs

SERIAL I/O

WDT

PSM

TIC

PWM

8-CHANNEL

12-BIT ADC

4-kBYTE

ELECTRICALLY

REPROGRAMMABLE

NONVOLATILE

FLASH/EE DATA

MEMORY

2304 BYTES

RAM

03260-0-024

Figure 26. Programming Model

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 21 of 88

ACCUMULATOR SFR (ACC)

ACC is the accumulator register and is used for math opera-

tions including addition, subtraction, integer multiplication and

division, and Boolean bit manipulations. The mnemonics for

accumulator-specific instructions refer to the accumulator as A.

B SFR (B)

The B register is used with the ACC for multiplication and

division operations. For other instructions, it can be treated as a

general-purpose scratchpad register.

Stack Pointer (SP and SPH)

The SP SFR is the stack pointer and is used to hold an internal

RAM address that is called the top of the stack. The SP register

is incremented before data is stored during PUSH and CALL

executions. While the stack may reside anywhere in on-chip

RAM, the SP register is initialized to 07H after a reset, which

causes the stack to begin at location 08H.

As mentioned earlier, the parts offer an extended 11-bit stack

pointer. The 3 extra bits used to make up the 11-bit stack

pointer are the 3 LSBs of the SPH byte located at B7H.

Data Pointer (DPTR)

The data pointer is made up of three 8-bit registers named DPP

(page byte), DPH (high byte), and DPL (low byte). These are

used to provide memory addresses for internal and external

code access and for external data access. They may be manipu-

lated as a 16-bit register (DPTR = DPH, DPL), although INC

DPTR instructions automatically carry over to DPP, or as three

independent 8-bit registers (DPP, DPH, DPL). The parts support

dual data pointers. Refer to the Dual Data Pointer section.

Program Status Word (PSW)

The PSW SFR contains several bits reflecting the current status

of the CPU, as detailed in Table 5.

SFR Address D0H

Power-On Default 00H

Bit Addressable Yes

Table 5. PSW SFR Bit Designations

Bit Name Description

7 CY Carry Flag.

6 AC Auxiliary Carry Flag.

5 F0 General-Purpose Flag.

4 RS1 Register Bank Select Bits.

3 RS0 RS1

RS0

Selected Bank

2 OV Overflow Flag.

1 F1 General-Purpose Flag.

0 P Parity Bit.

Power Control SFR (PCON)

The PCON SFR contains bits for power-saving options and

general-purpose status flags, as shown in Table 6.

SFR Address 87H

Power-On Default 00H

Bit Addressable No

Table 6. PCON SFR Bit Designations

Bit No. Name Description

7 SMOD Double UART Baud Rate.

6 SERIPD I2C/SPI Power-Down Interrupt Enable.

5 INT0PD

INT0 Power-Down Interrupt Enable.

4 ALEOFF Disable ALE Output.

3 GF1 General-Purpose Flag Bit.

2 GF0 General-Purpose Flag Bit.

1 PD Power-Down Mode Enable.

0 IDL Idle Mode Enable.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 22 of 88

SPECIAL FUNCTION REGISTER BANKS

All registers except the program counter and the four general-

purpose register banks reside in the special function register

(SFR) area. The SFR registers include control, configuration,

and data registers, which provide an interface between the CPU

and other on-chip peripherals. Figure 27 shows a full SFR

memory map and SFR contents on reset. Unoccupied SFR

locations are shown dark-shaded in the figure (NOT USED).

Unoccupied locations in the SFR address space are not

implemented, i.e., no register exists at this location. If an

unoccupied location is read, an unspecified value is returned.

SFR locations reserved for on-chip testing are shown lighter

shaded (RESERVED) and should not be accessed by user

software. Sixteen of the SFR locations are also bit addressable

and denoted by 1 in Figure 27, i.e., the bit addressable SFRs are

those whose address ends in 0H or 8H.

SPICON

F8H

04H

DAC0L

F9H 00H

DAC0H

FAH 00H

DAC1L

FBH 00H

DAC1H

FCH 00H

DACCON

FDH 04H

RESERVED

F0H 00H

ADCOFSL

F1H 00H

ADCOFSH

F2H 20H

ADCGAINL

F3H 00H

ADCGAINH

F4H 00H

ADCCON3

F5H 00H RESERVED

I2CCON

E8H 00H RESERVED

ACC

E0H 00H

RESERVED

ADCCON2

D8H 00H

ADCDATAL

D9H 00H

ADCDATAH

DAH 00H RESERVED

PSW

D0H 00H

DMAL

D2H 00H

DMAH

D3H 00H

DMAP

D4H 00H RESERVED

T2CON

C8H 00H

RCAP2L

CAH 00H

RCAP2H

CBH 00H

TL2

CCH 00H

TH2

CDH 00H RESERVED

WDCON

C0H 10H

B8H 00H

ECON

B9H 00H

EDATA1

BCH 00H

EDATA2

BDH 00H

A8H 00H

IEIP2

A9H A0H

A0H FFH

SCON

98H 00H

SBUF

99H 00H

I2CDAT

9AH 00H NOT USED

1, 2

90H FFH NOT USED

TCON

88H 00H

TMOD

89H 00H

TL0

8AH 00H

TL1

8BH 00H

TH0

8CH 00H

TH1

8DH 00H

80H FFH

81H 07H

DPL

82H 00H

DPH

83H 00H

DPP

84H 00H

RESERVEDRESERVEDRESERVEDRESERVEDRESERVED

RESERVEDRESERVEDRESERVED

RESERVEDRESERVED

RESERVED

NOT USED

NOT USEDNOT USED

B0H FFH

NOT USEDNOT USED

SPIDAT

F7H 00H

ADCCON1

EFH 40H

RESERVED

PSMCON

DFH DEH

EDARL

C6H 00H

EDATA3

BEH 00H

EDATA4

BFH 00H

NOT USED

PCON

87H 00H

ISPI

FFH

WCOL

FEH 0

SPE

FDH 0

SPIM

FCH 0

CPOL

FBH 0

CPHA

FAH

SPR1

F9H 0

SPR0

F8H

BITS

F7H 0 F6H 0 F5H 0 F4H 0 F3H 0 F2H F1H 0 F0H 0

BITS

I2CSI/MDO

EFH

EEH 0

I2C1O1MCO

EDH 0 ECH 0 EBH 0 EAH E9H 0 E8H 0

BITS

E7H 0 E6H 0 E5H 0 E4H 0 E3H 0 E2H E1H 0 E0H 0

BITS

ADCI

DFH

DMA

DEH 0

CCONV

DDH 0

SCONV

DCH 0

CS3

DBH 0

CS2

DAH

CS1

D9H 0

CS0

D8H

BITS

D7H 0

D6H 0

D5H 0

RS1

D4H 0

RS0

D3H 0

D2H

D1H 0

D0H 0

BITS

TF2

CFH 0

EXF2

CEH 0

RCLK

CDH 0

TCLK

CCH 0

EXEN2

CBH 0

TR2

CAH

CNT2

C9H 0

CAP2

C8H 0

BITS

PRE3

C7H 0

PRE2

C6H 0

PRE1

C5H 0 C4H 1

WDIR

C3H 0

WDS

C2H

WDE

C1H 0

WDWR

C0H 0

BITS

PSI

BFH 0

PADC

BEH 0

PT2

BDH 0

BCH 0

PT1

BBH 0

PX1

BAH

PT0

B9H 0

PX0

B8H 0

BITS

B7H 1

B6H 1

B5H 1

B4H 1

INT1

B3H 1

INT0

B2H

TxD

B1H 1

RxD

B0H 1

BITS

AFH

EADC

AEH

ET2

ADH

ACH 0

ET1

ABH 0

EX1

AAH

ET0

A9H 0

EX0

A8H 0

BITS

A7H A6H A5H 1 A4H 1 A3H 1 A2H A1H 1 A0H 1

BITS

SM0

9FH 0

SM1

9EH 0

SM2

9DH 0

REN

9CH 0

TB8

9BH 0

RB8

9AH

99H 0

98H 0

BITS

97H 1 96H 1 95H 1 94H 1 93H 1 92H

T2EX

91H 1

90H 1

BITS

TF1

8FH 0

TR1

8EH 0

TF0

8DH 0

TR0

8CH 0

IE1

8BH 0

IT1

8AH

IE0

89H 0

IT0

88H 0

BITS

87H 1 86H 1 85H 1 84H 1 83H 1 82H 81H 1 80H 1

BITS

IE0

89H 0

IT0

88H 0

TCON

88H 00H

MNEMONIC

SFR ADDRESS

DEFAULT VALUE

MNEMONIC

DEFAULT VALUE

SFR ADDRESS

THESE BITS ARE CONTAINED IN THIS BYTE.

SFR MAP KEY:

NOTES

SFRs WHOSE ADDRESS ENDS IN 0H OR 8H ARE BIT ADDRESSABLE.

THE PRIMARY FUNCTION OF PORT1 IS AS AN ANALOG INPUT PORT; THEREFORE, TO ENABLE THE DIGITAL SECONDARY FUNCTIONS ON THESE

PORT PINS, WRITE A 0 TO THE CORRESPONDING PORT 1 SFR BIT.

CALIBRATION COEFFICIENTS ARE PRECONFIGURED ON POWER-UP TO FACTORY CALIBRATED VALUES.

RESERVEDRESERVED

RESERVED

000

TIMECON HTHSEC SEC MIN HOUR INTVAL DPCON

A1H A2H A3H A4H A5H A6H A7H

00H 00H 00H 00H 00H 00H 00H

RESERVED RESERVED RESERVED RESERVED

RESERVED RESERVED

PWMCON

AEH 00H

CFG841/

CFG842

AFH 00H

RESERVED RESERVED

T3FD T3CON

9DH 9EH00H 00H

PWM0L PWM0H PWM1L PWM1H SPH

00H 00H 00H 00H 00HB1H B2H B3H B4H B7H

RESERVED RESERVED RESERVED

CHIPID

C2H XXH

EDARH

C7H 00H

I2CGC/MDE

I2CM

RESERVED

PRE0

PLLCON

D7H 53H

I2C1O0/MDI

I2CRS I2CTX I2CI

I2CADD

9BH 55H

03260-0-025

I2CADD1

91H 7FH

I2CADD2

92H 7FH

I2CADD3

93H 7FH

Figure 27. Special Function Register Locations and Reset Values

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 23 of 88

ADC CIRCUIT INFORMATION

General Overview

The ADC conversion block incorporates a fast, 8-channel,

12-bit, single-supply ADC. This block provides the user with

multichannel mux, track-and-hold, on-chip reference, calibra-

tion features, and ADC. All components in this block are easily

configured via a 3-register SFR interface.

The ADC converter consists of a conventional successive

approximation converter based around a capacitor DAC. The

converter accepts an analog input range of 0 V to VREF. A high

precision, 15 ppm, low drift, factory calibrated 2.5 V reference is

provided on-chip. An external reference can be connected as

described in the Voltage Reference Connections section. This

external reference can be in the range 1 V to AVDD.

Single-step or continuous conversion modes can be initiated in

software or alternatively by applying a convert signal to an

external pin. Timer 2 can also be configured to generate a

repetitive trigger for ADC conversions. The ADC may be

configured to operate in a DMA mode whereby the ADC block

continuously converts and captures samples to an external

RAM space without any interaction from the MCU core. This

automatic capture facility can extend through a 16 MByte

external data memory space.

The ADuC841/ADuC842/ADuC843 are shipped with factory

programmed calibration coefficients that are automatically

downloaded to the ADC on power-up, ensuring optimum ADC

performance. The ADC core contains internal offset and gain

calibration registers that can be hardware calibrated to

minimize system errors.

A voltage output from an on-chip band gap reference propor-

tional to absolute temperature can also be routed through the

front end ADC multiplexer (effectively a 9th ADC channel

input), facilitating a temperature sensor implementation.

ADC Transfer Function

The analog input range for the ADC is 0 V to VREF. For this

range, the designed code transitions occur midway between

successive integer LSB values, i.e., 0.5 LSB, 1.5 LSB, 2.5 LSB . . .

FS –1.5 LSB. The output coding is straight binary with 1 LSB =

FS/4096 or 2.5 V/4096 = 0.61 mV when VREF = 2.5 V. The ideal

input/output transfer characteristic for the 0 V to VREF range is

shown in Figure 28.

OUTPUT

CODE

111...111

111...110

111...101

111...100

000...011

000...010

000...001

000...000

0V 1LSB +FS

1LSB = FS

4096

03260-0-026

Figure 28. ADC Transfer Function

Typical Operation

Once configured via the ADCCON 1–3 SFRs, the ADC converts

the analog input and provides an ADC 12-bit result word in the

ADCDATAH/L SFRs. The top 4 bits of the ADCDATAH SFR

are written with the channel selection bits to identify the channel

result. The format of the ADC 12-bit result word is shown in

Figure 29.

CH–ID

TOP 4 BITS HIGH 4 BITS OF

ADC RESULT WORD

LOW 8 BITS OF THE

ADC RESULT WORD

ADCDATAH SFR

ADCDATAL SFR

03260-0-027

Figure 29. ADC Result Word Format

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 24 of 88

ADCCON1—(ADC Control SFR 1)

The ADCCON1 register controls conversion and acquisition

times, hardware conversion modes, and power-down modes as

detailed below.

SFR Address EFH

SFR Power-On Default 40H

Bit Addressable No

Table 7. ADCCON1 SFR Bit Designations

Bit No. Name Description

7 MD1 The mode bit selects the active operating mode of the ADC.

Set by the user to power up the ADC.

Cleared by the user to power down the ADC.

6 EXT_REF Set by the user to select an external reference.

Cleared by the user to use the internal reference.

The ADC clock divide bits (CK1, CK0) select the divide ratio for the PLL master clock (ADuC842/ADuC843) or the

external crystal (ADuC841) used to generate the ADC clock. To ensure correct ADC operation, the divider ratio

must be chosen to reduce the ADC clock to 8.38 MHz or lower. A typical ADC conversion requires 16 ADC clocks

plus the selected acquisition time.

The divider ratio is selected as follows:

CK1

CK0

CK1

CK0

MCLK Divider

4 (Do not use with a CD setting of 0)

The ADC acquisition select bits (AQ1, AQ0) select the time provided for the input track-and-hold amplifier to

acquire the input signal. An acquisition of three or more ADC clocks is recommended; clocks are as follows:

AQ1

AQ0

AQ1

AQ0

No. ADC Clks

1 T2C

The Timer 2 conversion bit (T2C) is set by the user to enable the Timer 2 overflow bit to be used as the ADC

conversion start trigger input.

0 EXC

The external trigger enable bit (EXC) is set by the user to allow the external Pin P3.5 (CONVST) to be used as the

active low convert start input. This input should be an active low pulse (minimum pulse width >100 ns) at the

required sample rate.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 25 of 88

ADCCON2—(ADC Control SFR 2)

The ADCCON2 register controls ADC channel selection and

conversion modes as detailed below.

SFR Address D8H

SFR Power-On Default 00H

Bit Addressable Yes

Table 8. ADCCON2 SFR Bit Designations

Bit No. Name Description

7 ADCI ADC Interrupt Bit.

Set by hardware at the end of a single ADC conversion cycle or at the end of a DMA block conversion.

Cleared by hardware when the PC vectors to the ADC interrupt service routine. Otherwise, the ADCI bit is cleared

by user code.

6 DMA DMA Mode Enable Bit.

Set by the user to enable a preconfigured ADC DMA mode operation. A more detailed description of this mode is

given in the ADC DMA Mode section. The DMA bit is automatically set to 0 at the end of a DMA cycle. Setting this

bit causes the ALE output to cease; it will start again when DMA is started and will operate correctly after DMA is

complete.

5 CCONV Continuous Conversion Bit.

Set by the user to initiate the ADC into a continuous mode of conversion. In this mode, the ADC starts converting

based on the timing and channel configuration already set up in the ADCCON SFRs; the ADC automatically starts

another conversion once a previous conversion has completed.

4 SCONV Single Conversion Bit.

Set to initiate a single conversion cycle. The SCONV bit is automatically reset to 0 on completion of the single

conversion cycle.

CS3

CS2

CS1

CS0

Channel Selection Bits.

Allow the user to program the ADC channel selection under software control. When a conversion is initiated, the

converted channel is the one pointed to by these channel selection bits. In DMA mode, the channel selection is

derived from the channel ID written to the external memory.

CS3

CS2

CS1

CS0

CH#

Temp Monitor

DAC0

DAC1

AGND

VREF

DMA STOP

Requires minimum of 1 µs to acquire.

Only use with internal DAC output buffer on.

Place in XRAM location to finish DMA sequence; refer to

the ADC DMA Mode section.

All other combinations reserved.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 26 of 88

ADCCON3—(ADC Control SFR 3)

The ADCCON3 register controls the operation of various

calibration modes and also indicates the ADC busy status.

SFR Address F5H

SFR Power-On Default 00H

Bit Addressable No

Table 9. ADCCON3 SFR Bit Designations

Bit No. Name Description

7 BUSY ADC Busy Status Bit.

A read-only status bit that is set during a valid ADC conversion or during a calibration cycle.

Busy is automatically cleared by the core at the end of conversion or calibration.

6 RSVD Reserved. This bit should always be written as 0.

5 AVGS1 Number of Average Selection Bits.

This bit selects the number of ADC readings that are averaged during a calibration cycle. 4 AVGS0

AVGS1

AVGS0

Number of Averages

3 RSVD Reserved. This bit should always be written as 0.

2 RSVD This bit should always be written as 1 by the user when performing calibration.

1 TYPICAL Calibration Type Select Bit.

This bit selects between offset (zero-scale) and gain (full-scale) calibration.

Set to 0 for offset calibration.

Set to 1 for gain calibration.

0 SCAL Start Calibration Cycle Bit.

When set, this bit starts the selected calibration cycle.

It is automatically cleared when the calibration cycle is completed.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 27 of 88

The ADC incorporates a successive approximation architecture

(SAR) involving a charge-sampled input stage. Figure 30 shows

the equivalent circuit of the analog input section. Each ADC

conversion is divided into two distinct phases, as defined by the

position of the switches in Figure 30. During the sampling

phase (with SW1 and SW2 in the track position), a charge

proportional to the voltage on the analog input is developed

across the input sampling capacitor. During the conversion

phase (with both switches in the hold position), the capacitor

DAC is adjusted via internal SAR logic until the voltage on

Node A is 0, indicating that the sampled charge on the input

capacitor is balanced out by the charge being output by the

capacitor DAC. The final digital value contained in the SAR is

then latched out as the result of the ADC conversion. Control of

the SAR and timing of acquisition and sampling modes is

handled automatically by built-in ADC control logic.

Acquisition and conversion times are also fully configurable

under user control.

CAPACITOR

DAC

COMPARATOR

REF

AGND

DAC1

DAC0

TEMPERATURE MONITOR

AIN7

AIN0

32pF

AGND

ADuC841/ADuC842/ADuC843

NODE A

sw1

sw2

TRACK

HOLD

200Ω

03260-0-028

Figure 30. Internal ADC Structure

Note that whenever a new input channel is selected, a residual

charge from the 32 pF sampling capacitor places a transient on

the newly selected input. The signal source must be capable of

recovering from this transient before the sampling switches go

into hold mode. Delays can be inserted in software (between

channel selection and conversion request) to account for input

stage settling, but a hardware solution alleviates this burden

from the software design task and ultimately results in a cleaner

system implementation. One hardware solution is to choose a

very fast settling op amp to drive each analog input. Such an op

amp would need to fully settle from a small signal transient in

less than 300 ns in order to guarantee adequate settling under

all software configurations. A better solution, recommended for

use with any amplifier, is shown in Figure 31. Though at first

glance the circuit in Figure 31 may look like a simple antialias-

ing filter, it actually serves no such purpose since its corner

frequency is well above the Nyquist frequency, even at a 200

kHz sample rate. Though the R/C does help to reject some

incoming high frequency noise, its primary function is to ensure

that the transient demands of the ADC input stage are met.

AIN0

ADuC841/

ADuC842/

ADuC843

10Ω

0.1µF

03260-0-029

Figure 31. Buffering Analog Inputs

It does so by providing a capacitive bank from which the 32 pF

sampling capacitor can draw its charge. Its voltage does not

change by more than one count (1/4096) of the 12-bit transfer

function when the 32 pF charge from a previous channel is

dumped onto it. A larger capacitor can be used if desired, but

not a larger resistor (for reasons described below). The Schottky

diodes in Figure 31 may be necessary to limit the voltage

applied to the analog input pin per the Absolute Maximum

Ratings. They are not necessary if the op amp is powered from

the same supply as the part since in that case the op amp is

unable to generate voltages above VDD or below ground. An op

amp of some kind is necessary unless the signal source is very

low impedance to begin with. DC leakage currents at the parts’

analog inputs can cause measurable dc errors with external

source impedances as low as 100 Ω or so. To ensure accurate

ADC operation, keep the total source impedance at each analog

input less than 61 Ω. The Table 10 illustrates examples of how

source impedance can affect dc accuracy.

Table 10. Source Impedance and DC Accuracy

Source

Impedance Ω

Error from 1 µA

Leakage Current

Error from 10 µA

Leakage Current

61 61 µV = 0.1 LSB 610 µV = 1 LSB

610 610 µV = 1 LSB 6.1 mV = 10 LSB

Although Figure 31 shows the op amp operating at a gain of 1,

one can, of course, configure it for any gain needed. Also, one

can just as easily use an instrumentation amplifier in its place to

condition differential signals. Use an amplifier that is capable of

delivering the signal (0 V to VREF) with minimal saturation.

Some single-supply rail-to-rail op amps that are useful for this

purpose are described in Table 11. Check Analog Devices website

www.analog.com for details on these and other op amps and

instrumentation amps.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 28 of 88

Table 11. Some Single-Supply Op Amps

Op Amp Model Characteristics

OP281/OP481 Micropower

OP191/OP291/OP491 I/O Good up to VDD, Low Cost

OP196/OP296/OP496 I/O to VDD, Micropower, Low Cost

OP183/OP283 High Gain-Bandwidth Product

OP162/OP262/OP462 High GBP, Micro Package

AD820/AD822/AD824 FET Input, Low Cost

AD823 FET Input, High GBP

Keep in mind that the ADC’s transfer function is 0 V to VREF,

and that any signal range lost to amplifier saturation near

ground will impact dynamic range. Though the op amps in

Table 11 are capable of delivering output signals that very

closely approach ground, no amplifier can deliver signals all the

way to ground when powered by a single supply. Therefore, if a

negative supply is available, you might consider using it to

power the front end amplifiers. If you do, however, be sure to

include the Schottky diodes shown in Figure 31 (or at least the

lower of the two diodes) to protect the analog input from

undervoltage conditions. To summarize this section, use the

circuit in Figure 31 to drive the analog input pins of the parts.

Voltage Reference Connections

The on-chip 2.5 V band gap voltage reference can be used as the

reference source for the ADC and DACs. To ensure the accuracy

of the voltage reference, you must decouple the CREF pin to

ground with a 0.47 µF capacitor, as shown in Figure 32. Note

that this is different from the ADuC812/ADuC831/ADuC832.

BUFFER

BUFFER 0.47

Ω

REF

= NC

REF

2.5V

BAND GAP

REFERENCE

ADuC841/ADuC842/ADuC843

03260-0-030

Figure 32. Decoupling VREF and CREF

If the internal voltage reference is to be used as a reference for

external circuitry, the CREF output should be used. However, a

buffer must be used in this case to ensure that no current is

drawn from the CREF pin itself. The voltage on the CREF pin is that

of an internal node within the buffer block, and its voltage is

critical for ADC and DAC accuracy. The parts power up with

their internal voltage reference in the off state.

If an external voltage reference is preferred, it should be

connected to the CREF pin as shown in Figure 33. Bit 6 of the

ADCCON1 SFR must be set to 1 to switch in the external

reference voltage.

To ensure accurate ADC operation, the voltage applied to CREF

must be between 1 V and AVDD. In situations where analog

input signals are proportional to the power supply (such as in

some strain gage applications), it may be desirable to connect

the CREF pin directly to AVDD. Operation of the ADC or DACs

with a reference voltage below 1 V, however, may incur loss of

accuracy, eventually resulting in missing codes or non-

monotonicity. For that reason, do not use a reference voltage

lower than 1 V.

BUFFER

Ω

REF

EXTERNAL

VOLTAGE

REFERENCE

1 = EXTERNAL

0 = INTERNAL

0.1µF

2.5V

BAND GAP

REFERENCE

ADuC841/ADuC842/ADuC843

ADCCON1.6

03260-0-031

REF

= NC

Figure 33. Using an External Voltage Reference

Configuring the ADC

The parts’ successive approximation ADC is driven by a divided

down version of the master clock. To ensure adequate ADC

operation, this ADC clock must be between 400 kHz and

8.38 MHz. Frequencies within this range can be achieved easily

with master clock frequencies from 400 kHz to well above

16 MHz, with the four ADC clock divide ratios to choose from.

For example, set the ADC clock divide ratio to 8 (i.e., ADCCLK

= 16.777216 MHz/8 = 2 MHz) by setting the appropriate bits in

ADCCON1 (ADCCON1.5 = 1, ADCCON1.4 = 0). The total

ADC conversion time is 15 ADC clocks, plus 1 ADC clock for

synchronization, plus the selected acquisition time (1, 2, 3, or 4

ADC clocks). For the preceding example, with a 3-clock

acquisition time, total conversion time is 19 ADC clocks (or

9.05 µs for a 2 MHz ADC clock).

In continuous conversion mode, a new conversion begins each

time the previous one finishes. The sample rate is then simply

the inverse of the total conversion time described previously. In

the preceding example, the continuous conversion mode sample

rate is 110.3 kHz.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 29 of 88

If using the temperature sensor as the ADC input, the ADC

should be configured to use an ADCCLK of MCLK/32 and four

acquisition clocks.

Increasing the conversion time on the temperature monitor

channel improves the accuracy of the reading. To further

improve the accuracy, an external reference with low tempera-

ture drift should also be used.

ADC DMA Mode

The on-chip ADC has been designed to run at a maximum

conversion speed of 2.38 µs (420 kHz sampling rate). When

converting at this rate, the ADuC841/ADuC842/ADuC843

MicroConverter has 2 µs to read the ADC result and to store the

result in memory for further postprocessing; otherwise the next

ADC sample could be lost. In an interrupt driven routine, the

MicroConverter would also have to jump to the ADC interrupt

service routine, which also increases the time required to store

the ADC results. In applications where the parts cannot sustain

the interrupt rate, an ADC DMA mode is provided.

To enable DMA mode, Bit 6 in ADCCON2 (DMA) must be set,

which allows the ADC results to be written directly to a 16 MByte

external static memory SRAM (mapped into data memory

space) without any interaction from the core of the part. This

mode allows the part to capture a contiguous sample stream at

full ADC update rates (420 kHz).

Typical DMA Mode Configuration Example

Setting the parts to DMA mode consists of the following steps:

1. The ADC must be powered down. This is done by ensuring

that MD1 and MD0 are both set to 0 in ADCCON1.

2. The DMA address pointer must be set to the start address

of where the ADC results are to be written. This is done by

writing to the DMA mode address pointers DMAL, DMAH,

and DMAP. DMAL must be written to first, followed by

DMAH, and then by DMAP.

3. The external memory must be preconfigured. This consists

of writing the required ADC channel IDs into the top four

bits of every second memory location in the external

SRAM, starting at the first address specified by the DMA

address pointer. Because the ADC DMA mode operates

independently from the ADuC841/ADuC842/ADuC843

core, it is necessary to provide it with a stop command.

This is done by duplicating the last channel ID to be

converted followed by 1111 into the next channel selection

field. A typical preconfiguration of external memory is

shown in Figure 34.

11 11

00 11

100 0

010 1

00 10

00000AH

000000H CONVERT ADC CH 2

CONVERT ADC CH 5

CONVERT ADC CH 3

CONVERT TEMP SENSOR

STOP COMMAND

REPEAT LAST CHANNEL

FOR A VALID STOP

CONDITION

03260-0-033

Figure 34. Typical DMA External Memory Preconfiguration

4. The DMA is initiated by writing to the ADC SFRs in the

following sequence:

a. ADCCON2 is written to enable the DMA mode, i.e.,

MOV ADCCON2, #40H; DMA mode enabled.

b. ADCCON1 is written to configure the conversion

time and power-up of the ADC. It can also enable

Timer 2 driven conversions or external triggered

conversions if required.

c. ADC conversions are initiated. This is done by starting

single conversions, starting Timer 2, running for

Timer 2 conversions, or receiving an external trigger.

When the DMA conversions are complete, the ADC interrupt

bit, ADCI, is set by hardware, and the external SRAM contains

the new ADC conversion results as shown in Figure 35. Note

that no result is written to the last two memory locations.

When the DMA mode logic is active, it takes the responsibility

of storing the ADC results away from both the user and the core

logic of the part. As the DMA interface writes the results of the

ADC conversions to external memory, it takes over the external

memory interface from the core. Thus, any core instructions

that access the external memory while DMA mode is enabled

does not get access to the external memory. The core executes

the instructions, and they take the same time to execute, but

they cannot access the external memory.

1111

0011

1000

0101

0010

00000AH

000000H CONVERSION RESULT

FOR ADC CH 2

CONVERSION RESULT

FOR ADC CH 5

CONVERSION RESULT

FOR ADC CH 3

CONVERSION RESULT

FOR TEMP SENSOR

STOP COMMAND

NO CONVERSION

RESULT WRITTEN HERE

03260-0-034

Figure 35. Typical External Memory Configuration Post ADC DMA Operation

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 30 of 88

The DMA logic operates from the ADC clock and uses pipelin-

ing to perform the ADC conversions and to access the external

memory at the same time. The time it takes to perform one ADC

conversion is called a DMA cycle. The actions performed by the

logic during a typical DMA cycle are shown in Figure 36.

WRITE ADC RESULT

CONVERTED DURING

PREVIOUS DMA CYCLE

READ CHANNEL ID

TO BE CONVERTED DURING

NEXT DMA CYCLE

CONVERT CHANNEL READ DURING PREVIOUS DMA CYCLE

DMA CYCLE

03260-0-035

Figure 36. DMA Cycle

Figure 36 shows that during one DMA cycle, the following

actions are performed by the DMA logic:

1. An ADC conversion is performed on the channel whose ID

was read during the previous cycle.

2. The 12-bit result and the channel ID of the conversion

performed in the previous cycle is written to the external

memory.

3. The ID of the next channel to be converted is read from

external memory.

For the previous example, the complete flow of events is shown

in Figure 36. Because the DMA logic uses pipelining, it takes

three cycles before the first correct result is written out.

Micro Operation during ADC DMA Mode

During ADC DMA mode, the MicroConverter core is free to

continue code execution, including general housekeeping and

communication tasks. However, note that MCU core accesses to

Ports 0 and 2 (which of course are being used by the DMA con-

troller) are gated off during the ADC DMA mode of operation.

This means that even though the instruction that accesses the

external Ports 0 or 2 appears to execute, no data is seen at these

external ports as a result. Note that during DMA to the inter-

nally contained XRAM, Ports 0 and 2 are available for use.

The only case in which the MCU can access XRAM during

DMA is when the internal XRAM is enabled and the section of

RAM to which the DMA ADC results are being written to lies

in an external XRAM. Then the MCU can access the internal

XRAM only. This is also the case for use of the extended stack

pointer.

The MicroConverter core can be configured with an interrupt

to be triggered by the DMA controller when it has finished

filling the requested block of RAM with ADC results, allowing

the service routine for this interrupt to postprocess data without

any real-time timing constraints.

ADC Offset and Gain Calibration Coefficients

The ADuC841/ADuC842/ADuC843 have two ADC calibration

coefficients, one for offset calibration and one for gain calibra-

tion. Both the offset and gain calibration coefficients are 14-bit

words, and are each stored in two registers located in the special

function register (SFR) area. The offset calibration coefficient is

divided into ADCOFSH (six bits) and ADCOFSL (8 bits), and

the gain calibration coefficient is divided into ADCGAINH

(6 bits) and ADCGAINL (8 bits).

The offset calibration coefficient compensates for dc offset

errors in both the ADC and the input signal. Increasing the

offset coefficient compensates for positive offset, and effectively

pushes the ADC transfer function down. Decreasing the offset

coefficient compensates for negative offset, and effectively

pushes the ADC transfer function up. The maximum offset that

can be compensated is typically ±5% of VREF, which equates to

typically ±125 mV with a 2.5 V reference.

Similarly, the gain calibration coefficient compensates for dc

gain errors in both the ADC and the input signal. Increasing the

gain coefficient compensates for a smaller analog input signal

range and scales the ADC transfer function up, effectively

increasing the slope of the transfer function. Decreasing the

gain coefficient compensates for a larger analog input signal

range and scales the ADC transfer function down, effectively

decreasing the slope of the transfer function. The maximum

analog input signal range for which the gain coefficient can

compensate is 1.025 × VREF, and the minimum input range is

0.975 × VREF, which equates to typically ±2.5% of the reference

voltage.

CALIBRATING THE ADC

Two hardware calibration modes are provided, which can be

easily initiated by user software. The ADCCON3 SFR is used to

calibrate the ADC. Bit 1 (typical) and CS3 to CS0 (ADCCON2) set

up the calibration modes.

Device calibration can be initiated to compensate for significant

changes in operating condition frequency, analog input range,

reference voltage, and supply voltages. In this calibration mode,

offset calibration uses internal AGND selected via ADCCON2

nal VREF selected by Bits CS3 to CS0 (1100). Offset calibration

should be executed first, followed by gain calibration. System

calibration can be initiated to compensate for both internal and

external system errors. To perform system calibration by using

an external reference, tie the system ground and reference to

any two of the six selectable inputs. Enable external reference

mode (ADCCON1.6). Select the channel connected to AGND

via Bits CS3 to CS0 and perform system offset calibration. Select

the channel connected to VREF via Bits CS3 to CS0 and perform

system gain calibration.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 31 of 88

Initiating the Calibration in Code

When calibrating the ADC using ADCCON1, the ADC must be

set up into the configuration in which it will be used. The

ADCCON3 register can then be used to set up the device and to

calibrate the ADC offset and gain.

MOV ADCCON1,#08CH ; ADC on; ADCCLK set

;to divide by 32,4

;acquisition clock

To calibrate devic e offset:

MOV ADCCON2,#0BH ;select internal AGND

MOV ADCCON3,#25H ;select offset calibration,

;31 averages per bit,

;offset calibration

To calibrate devic e gain :

MOV ADCCON2,#0CH ;select internal VREF

MOV ADCCON3,#27H ;select offset calibration,

;31 averages per bit,

;offset calibration

To calibrate system offset, connect system AGND to an ADC

channel input (0).

MOV ADCCON2,#00H ;select external AGND

MOV ADCCON3,#25H ;select offset calibration,

;31 averages per bit

To calibrate system gain, connect system VREF to an ADC

channel input (1).

MOV ADCCON2,#01H ;select external VREF

MOV ADCCON3,#27H ;select offset calibration,

;31 averages per bit,

;offset calibration

The calibration cycle time TCAL is calculated by the following

equation:

(

)

ACQCAL TNUMAVADCCLKT +×××= 1614

For an ADCCLK/FCORE divide ratio of 32, TACQ = 4 ADCCLK,

and NUMAV = 15, the calibration cycle time is

()()

msT

CAL

41615524288/114

+×××=

In a calibration cycle, the ADC busy flag (Bit 7), instead of

framing an individual ADC conversion as in normal mode, goes

high at the start of calibration and returns to zero only at the

end of the calibration cycle. It can therefore be monitored in

code to indicate when the calibration cycle is completed. The

following code can be used to monitor the BUSY signal during

a calibration cycle:

WAIT:

MOV A, ADCCON3 ;move ADCCON3 to A

JB ACC.7, WAIT ;If Bit 7 is set jump to

WAIT else continue

NONVOLATILE FLASH/EE MEMORY

The ADuC841/ADuC842/ADuC843 incorporate Flash/EE

memory technology on-chip to provide the user with nonvola-

tile, in-circuit, reprogrammable code and data memory space.

Flash/EE memory is a relatively recent type of nonvolatile

memory technology, which is based on a single transistor cell

architecture. Flash/EE memory combines the flexible in-circuit

reprogrammable features of EEPROM with the space efficient/

density features of EPROM as shown in Figure 37.

Because Flash/EE technology is based on a single transistor cell

architecture, a flash memory array, such as EPROM, can be

implemented to achieve the space efficiencies or memory densities

required by a given design. Like EEPROM, flash memory can be

programmed in-system at a byte level; it must first be erased,

the erase being performed in page blocks. Thus, flash memory

is often and more correctly referred to as Flash/EE memory.

EEPROM

TECHNOLOGY

EPROM

TECHNOLOGY

FLASH/EEMEMORY

TECHNOLOGY

IN-CIRCUIT

REPROGRAMMABLE

PACE EFFICIENT

DENSITY

03260-0-036

Figure 37. Flash/EE Memory Development

Overall, Flash/EE memory represents a step closer to the ideal

memory device that includes nonvolatility, in-circuit program-

mability, high density, and low cost. Incorporated in the parts,

Flash/EE memory technology allows the user to update program

code space in-circuit, without the need to replace one-time

programmable (OTP) devices at remote operating nodes.

Flash/EE Memory and the ADuC841/ADuC842/ADuC843

The parts provide two arrays of Flash/EE memory for user

applications. Up to 62 kBytes of Flash/EE program space are

provided on-chip to facilitate code execution without any

external discrete ROM device requirements. The program

memory can be programmed in-circuit by using the serial

download mode provided, by using conventional third party

memory programmers, or via a user defined protocol that can

configure it as data if required.

Note that the following sections use the 62 kByte program space

as an example when referring to ULOAD mode. For the other

memory models (32 kByte and 8 kByte), the ULOAD space

moves to the top 8 kBytes of the on-chip program memory, i.e.,

for 32 kBytes, the ULOAD space is from 24 kBytes to 32 kBytes,

the kernel still resides in a protected space from 60 kBytes to

62 kBytes. There is no ULOAD space present on the 8 kBtye part.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 32 of 88

A 4 kByte Flash/EE data memory space is also provided on-

chip. This may be used as a general-purpose nonvolatile

scratchpad area. User access to this area is via a group of six

SFRs. This space can be programmed at a byte level, although it

must first be erased in 4-byte pages.

Flash/EE Memory Reliability

The Flash/EE program and data memory arrays on the parts are

fully qualified for two key Flash/EE memory characteristics:

Flash/EE memory cycling endurance and Flash/EE memory

data retention.

Endurance quantifies the ability of the Flash/EE memory to be

cycled through many program, read, and erase cycles. In real

terms, a single endurance cycle is composed of four independ-

ent, sequential events, defined as

1. Initial page erase sequence.

2. Read/verify sequence a single Flash/EE.

3. Byte program sequence memory.

4. Second read/verify sequence endurance cycle.

In reliability qualification, every byte in both the program and

data Flash/EE memory is cycled from 00H to FFH until a first

fail is recorded, signifying the endurance limit of the on-chip

Flash/EE memory.

As indicated in the Specifications table, the parts’ Flash/EE

memory endurance qualification has been carried out in

accordance with JEDEC Retention Lifetime Specification A117

over the industrial temperature range of –40°C to +25°C and

+25°C to +85°C. The results allow the specification of a mini-

mum endurance figure over supply and over temperature of

100,000 cycles, with an endurance figure of 700,000 cycles being

typical of operation at 25°C.

Retention quantifies the ability of the Flash/EE memory to

retain its programmed data over time. Again, the parts have

been qualified in accordance with the formal JEDEC Retention

Lifetime Specification (A117) at a specific junction temperature

(TJ = 55°C). As part of this qualification procedure, the Flash/EE

memory is cycled to its specified endurance limit, described

previously, before data retention is characterized. This means

that the Flash/EE memory is guaranteed to retain its data for its

fully specified retention lifetime every time the Flash/EE

memory is reprogrammed. Also note that retention lifetime,

based on an activation energy of 0.6 eV, derates with TJ as

shown in Figure 38.

40 60 70 90

JUNCTION TEMPERATURE (°C)

RETENTION

(Years)

250

200

150

100

050 80 110

300

100

ADI SPECIFICATION

100 YEARS MIN.

AT T

= 55°C

03260-0-037

Figure 38. Flash/EE Memory Data Retention

Using the Flash/EE Program Memory

The 62 kByte Flash/EE program memory array is mapped into

the lower 62 kBytes of the 64 kByte program space addressable

by the parts, and is used to hold user code in typical applica-

tions. The program Flash/EE memory array can be

programmed in three ways:

Serial Downloading (In-Circuit Programming)

The parts facilitate code download via the standard UART serial

port. The parts enter serial download mode after a reset or

power cycle if the PSEN pin is pulled low through an external

1 kΩ resistor. Once in serial download mode, the user can

download code to the full 62 kBytes of Flash/EE program

memory while the device is in-circuit in its target application

hardware.

A PC serial download executable is provided as part of the

ADuC841/ADuC842 QuickStart development system. The

serial download protocol is detailed in MicroConverter

Application Note uC004.

Parallel Programming

Parallel programming mode is fully compatible with conven-

tional third party flash or EEPROM device programmers. In

this mode, Ports P0, P1, and P2 operate as the external data and

address bus interface, ALE operates as the write enable strobe,

and Port P3 is used as a general configuration port, which

configures the device for various program and erase operations

during parallel programming. The high voltage (12 V) supply

required for flash programming is generated using on-chip

charge pumps to supply the high voltage program lines. The

complete parallel programming specification is available on the

MicroConverter home page at www.analog.com/microconverter.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 33 of 88

User Download Mode (ULOAD)

Figure 39 shows that it is possible to use the 62 kBytes of

Flash/EE program memory available to the user as a single

block of memory. In this mode, all of the Flash/EE memory is

read-only to user code.

However, the Flash/EE program memory can also be written to

during runtime simply by entering ULOAD mode. In ULOAD

mode, the lower 56 kBytes of program memory can be erased and

reprogrammed by user software as shown in Figure 39. ULOAD

mode can be used to upgrade your code in the field via any user

defined download protocol. By configuring the SPI port on the

part as a slave, it is possible to completely reprogram the

56 kBytes of Flash/EE program memory in only 5 seconds (refer

to Application Note uC007).

Alternatively, ULOAD mode can be used to save data to the

56 kBytes of Flash/EE memory. This can be extremely useful in

data logging applications where the part can provide up to

60 kBytes of NV data memory on chip (4 kBytes of dedicated

Flash/EE data memory also exist).

The upper 6 kBytes of the 62 kBytes of Flash/EE program

memory are programmable only via serial download or parallel

programming. This means that this space appears as read-only

to user code. Therefore, it cannot be accidentally erased or

reprogrammed by erroneous code execution, which makes it

very suitable to use the 6 kBytes as a bootloader.

A bootload enable option exists in the serial downloader to

“always run from E000H after reset.” If using a bootloader, this

option is recommended to ensure that the bootloader always

executes correct code after reset. Programming the Flash/EE

program memory via ULOAD mode is described in more detail

in the description of ECON and in Application Note uC007.



EMBEDDED DOWNLOAD/DEBUG KERNEL

PERMANENTLY EMBEDDED FIRMWARE ALLOWS

CODE TO BE DOWNLOADED TO ANY OF THE

62 kBYTES OF ON-CHIP PROGRAM MEMORY.

THE KERNEL PROGRAM APPEARS AS 'NOP'

INSTRUCTIONS TO USER CODE

USER BOOTLOADER SPACE

THE USER BOOTLOADER

SPACE CAN BE PROGRAMMED IN

DOWNLOAD/DEBUG MODE VIA THE

KERNEL BUT IS READ ONLY WHEN

EXECUTING USER CODE

USER DOWNLOADER SPACE

EITHER THE DOWNLOAD/DEBUG

KERNEL OR USER CODE (IN

ULOAD MODE) CAN PROGRAM

THIS SPACE

FFFFH

2kBYTE

F800H

F7FFH

6kBYTE

E000H

dFFFH

56kBYTE

0000H

03260-0-038

62 kBYTES

OF USER

CODE

MEMORY

Figure 39. Flash/EE Program Memory Map in ULOAD Mode

(62 kByte Part)



EMBEDDED DOWNLOAD/DEBUG KERNEL

PERMANENTLY EMBEDDED FIRMWARE ALLOWS

CODE TO BE DOWNLOADED TO ANY OF THE

32 kBYTES OF ON-CHIP PROGRAM MEMORY.

THE KERNEL PROGRAM APPEARS AS 'NOP'

INSTRUCTIONS TO USER CODE

USER BOOTLOADER SPACE

THE USER BOOTLOADER

SPACE CAN BE PROGRAMMED IN

DOWNLOAD/DEBUG MODE VIA THE

KERNEL BUT IS READ ONLY WHEN

EXECUTING USER CODE

USER DOWNLOADER SPACE

EITHER THE DOWNLOAD/DEBUG

KERNEL OR USER CODE (IN

ULOAD MODE) CAN PROGRAM

THIS SPACE

FFFFH

2kBYTE

F800H

F7FFH

NOP'S

8000H

5FFFH

26kBYTE

0000H

03260-0-039

7FFFH

8kBYTE

6000H

32 kBYTES

OF USER

CODE

MEMORY

Figure 40. Flash/EE Program Memory Map in ULOAD Mode

(32 kByte Part)

Flash/EE Program Memory Security

The ADuC841/ADuC842/ADuC843 facilitate three modes of

Flash/EE program memory security. These modes can be

independently activated, restricting access to the internal code

space. These security modes can be enabled as part of serial

download protocol as described in Application Note uC004 or

via parallel programming. The security modes available on the

parts are as follows:

Lock Mode

This mode locks the code memory, disabling parallel program-

ming of the program memory. However, reading the memory in

parallel mode and reading the memory via a MOVC command

from external memory is still allowed. This mode is deactivated

by initiating a code-erase command in serial download or

parallel programming modes.

Secure Mode

This mode locks code in memory, disabling parallel program-

ming (program and verify/read commands) as well as disabling

the execution of a MOVC instruction from external memory,

which is attempting to read the op codes from internal memory.

Read/write of internal data Flash/EE from external memory is

also disabled. This mode is deactivated by initiating a code-erase

command in serial download or parallel programming modes.

Serial Safe Mode

This mode disables serial download capability on the device. If

serial safe mode is activated and an attempt is made to reset the

part into serial download mode, i.e., RESET asserted and de-

asserted with PSEN low, the part interprets the serial download

reset as a normal reset only. It therefore cannot enter serial

download mode but can only execute as a normal reset

sequence. Serial safe mode can be disabled only by initiating a

code-erase command in parallel programming mode.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 34 of 88

USING FLASH/EE DATA MEMORY

The 4 kBytes of Flash/EE data memory are configured as 1024

pages, each of 4 bytes. As with the other ADuC841/ADuC842/

ADuC843 peripherals, the interface to this memory space is via

a group of registers mapped in the SFR space. A group of four

data registers (EDATA1–4) is used to hold the four bytes of data

at each page. The page is addressed via the two registers, EADRH

and EADRL. Finally, ECON is an 8-bit control register that may

be written with one of nine Flash/EE memory access commands

to trigger various read, write, erase, and verify functions. A block

diagram of the SFR interface to the Flash/EE data memory array

is shown in Figure 41.

ECON—Flash/EE Memory Control SFR

Programming of either Flash/EE data memory or Flash/ EE

program memory is done through the Flash/EE memory

control SFR (ECON). This SFR allows the user to read, write,

erase, or verify the 4 kBytes of Flash/EE data memory or the

56 kBytes of Flash/EE program memory.

BYTE 1

(0000H)

EDATA1 SFR

BYTE 1

(0004H)

BYTE 1

(0008H)

BYTE 1

(000CH)

BYTE 1

(0FF8H)

BYTE 1

(0FFCH)

BYTE 2

(0001H)

EDATA2 SFR

BYTE 2

(0005H)

BYTE 2

(0009H)

BYTE 2

(000DH)

BYTE 2

(0FF9H)

BYTE 2

(0FFDH)

BYTE 3

(0002H)

EDATA3 SFR

BYTE 3

(0006H)

BYTE 3

(000AH)

BYTE 3

(000EH)

BYTE 3

(0FFAH)

BYTE 3

(0FFEH)

BYTE 4

(0003H)

EDATA4 SFR

BYTE 4

(0007H)

BYTE 4

(000BH)

BYTE 4

(000FH)

BYTE 4

(0FFBH)

(0FFFH)

01H

00H

02H

03H

3FEH

3FFH

PAGE ADDRESS

(EADRH/L)

BYTE

ADDRESSES

ARE GIVEN IN

BRACKETS

03260-0-040

BYTE 4

Figure 41. Flash/EE Data Memory Control and Configuration

Table 12. ECON—Flash/EE Memory Commands

ECON VALUE

Command Description (Normal Mode)

(Power-On Default)

Command Description (ULOAD Mode)

01H

READ

Results in 4 bytes in the Flash/EE data memory, addressed

by the page address EADRH/L, being read into EDATA1–4.

Not implemented. Use the MOVC instruction.

02H

WRITE

Results in 4 bytes in EDATA1–4 being written to the

Flash/EE data memory at the page address given by

EADRH/L (0 – EADRH/L < 0400H).

Note that the 4 bytes in the page being addressed must

be pre-erased.

Results in bytes 0–255 of internal XRAM being written to

the 256 bytes of Flash/EE program memory at the page

address given by EADRH (0 – EADRH < E0H).

Note that the 256 bytes in the page being addressed must

be pre-erased.

03H Reserved. Reserved.

04H

VERIFY

Verifies that the data in EDATA1–4 is contained in the

page address given by EADRH/L. A subsequent read of the

ECON SFR results in 0 being read if the verification is valid,

or a nonzero value being read to indicate an invalid

verification.

Not implemented. Use the MOVC and MOVX instructions

to verify the write in software.

05H

ERASE PAGE

Results in erasing the 4-byte page of Flash/EE data

memory addressed by the page address EADRH/L.

Results in the 64 byte page of Flash/EE program memory,

addressed by the byte address EADRH/L, being erased.

EADRL can equal any of 64 locations within the page. A

new page starts whenever EADRL is equal to 00H, 40H,

80H, or C0H.

06H

ERASE ALL

Results in erasing the entire 4 kBytes of Flash/EE data

memory.

Results in erasing the entire 56 kBytes of ULOAD Flash/EE

program memory.

81H

READBYTE

Results in the byte in the Flash/EE data memory,

addressed by the byte address EADRH/L, being read into

EDATA1 (0 – EADRH / L – 0FFFH).

Not implemented. Use the MOVC command.

82H

WRITEBYTE

Results in the byte in EDATA1 being written into Flash/EE

data memory at the byte address EADRH/L

Results in the byte in EDATA1 being written into Flash/EE

program memory at the byte address EADRH/L (0 –

EADRH/L – DFFFH).

0FH

EXULOAD

Leaves the ECON instructions to operate on the Flash/EE

data memory.

Enters normal mode directing subsequent ECON

instructions to operate on the Flash/EE data memory.

F0H

ULOAD

Enters ULOAD mode, directing subsequent ECON

instructions to operate on the Flash/EE program memory.

Leaves the ECON instructions to operate on the Flash/EE

program memory.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 35 of 88

Example: Programming the Flash/EE Data Memory

A user wants to program F3H into the second byte on Page 03H

of the Flash/EE data memory space while preserving the other

3 bytes already in this page. A typical program of the Flash/EE

data array involves

1. Setting EADRH/L with the page address.

2. Writing the data to be programmed to the EDATA1–4.

3. Writing the ECON SFR with the appropriate command.

Step 1: Set Up the Page Address

Address registers EADRH and EADRL hold the high byte

address and the low byte address of the page to be addressed.

The assembly language to set up the address may appear as

MOV EADRH,#0 ; Set Page Address Pointer

MOV EADRL,#03H

Step 2: Set Up the EDATA Registers

Write the four values to be written into the page into the four

SFRs, EDATA1–4. Unfortunately, the user does not know three

of them. Thus, the user must read the current page and over-

write the second byte.

MOV ECON,#1 ; Read Page into EDATA1-4

MOV EDATA2,#0F3H ; Overwrite byte 2

Step 3: Program Page

A byte in the Flash/EE array can be programmed only if it has

previously been erased. To be more specific, a byte can be

programmed only if it already holds the value FFH. Because of

the Flash/EE architecture, this erase must happen at a page level;

therefore, a minimum of 4 bytes (1 page) are erased when an

erase command is initiated. Once the page is erase, the user can

program the 4 bytes in-page and then perform a verification of

the data.

MOV ECON,#5 ; ERASE Page

MOV ECON,#2 ; WRITE Page

MOV ECON,#4 ; VERIFY Page

MOV A,ECON ; Check if ECON=0 (OK!)

JNZ ERROR

Although the 4 kBytes of Flash/EE data memory are shipped

from the factory pre-erased, i.e., byte locations set to FFH, it is

nonetheless good programming practice to include an

ERASEALL routine as part of any configuration/setup code

running on the parts. An ERASEALL command consists of

writing 06H to the ECON SFR, which initiates an erase of the

4-kByte Flash/EE array. This command coded in 8051 assembly

would appear as

MOV ECON,#06H ; Erase all Command

; 2 ms Duration

Flash/EE Memory Timing

Typical program and erase times for the parts are as follows:

Normal Mode (operating on Flash/EE data memory)

READPAGE (4 bytes) 22 machine cycles

WRITEPAGE (4 bytes) 380 µs

VERIFYPAGE (4 bytes) 22 machine cycles

ERASEPAGE (4 bytes) 2 ms

ERASEALL (4 kBytes) 2 ms

READBYTE (1 byte) 9 machine cycles

WRITEBYTE (1 byte) 200 µs

ULOAD Mode (operating on Flash/EE program memory)

WRITEPAGE (256 bytes) 16.5 ms

ERASEPAGE (64 bytes) 2 ms

ERASEALL (56 kBytes) 2 ms

WRITEBYTE (1 byte) 200 µs

Note that a given mode of operation is initiated as soon as the

command word is written to the ECON SFR. The core micro-

controller operation on the parts is idled until the requested

program/read or erase mode is completed. In practice, this

means that even though the Flash/EE memory mode of operation

is typically initiated with a two machine cycle MOV instruction

(to write to the ECON SFR), the next instruction is not executed

until the Flash/EE operation is complete. This means that the

core cannot respond to interrupt requests until the Flash/EE

operation is complete, although the core peripheral functions

like counter/timers continue to count and time as configured

throughout this period.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 36 of 88

ADuC842/ADuC843 Configuration SFR (CFG842)

The CFG842 SFR contains the necessary bits to configure the

internal XRAM, external clock select, PWM output selection,

DAC buffer, and the extended SP for both the ADuC842 and the

ADuC843. By default, it configures the user into 8051 mode, i.e.,

extended SP is disabled and internal XRAM is disabled. On the

ADuC841, this register is the CFG841 register and is described

on the next page.

CFG842 ADuC842/ADuC843 Config SFR

SFR Address AFH

Power-On Default 00H

Bit Addressable No

Table 13. CFG842 SFR Bit Designations

Bit No. Name Description

7 EXSP Extended SP Enable.

When set to 1 by the user, the stack rolls over from SPH/SP = 00FFH to 0100H.

When set to 0 by the user, the stack rolls over from SP = FFH to SP = 00H.

6 PWPO PWM Pin Out Selection.

Set to 1 by the user to select P3.4 and P3.3 as the PWM output pins.

Set to 0 by the user to select P2.6 and P2.7 as the PWM output pins.

5 DBUF DAC Output Buffer.

Set to 1 by the user to bypass the DAC output buffer.

Set to 0 by the user to enable the DAC output buffer.

4 EXTCLK Set by the user to 1 to select an external clock input on P3.4.

Set by the user to 0 to use the internal PLL clock.

3 RSVD Reserved. This bit should always contain 0.

2 RSVD Reserved. This bit should always contain 0.

1 MSPI Set to 1 by the user to move the SPI functionality of MISO, MOSI, and SCLOCK to P3.3, P3.4, and P3.5,

respectively.

Set to 0 by the user to leave the SPI functionality as usual on MISO, MOSI, and SCLOCK pins.

0 XRAMEN XRAM Enable Bit.

When set to 1 by the user, the internal XRAM is mapped into the lower 2 kBytes of the external address

space.

When set to 0 by the user, the internal XRAM is not accessible, and the external data memory is

mapped into the lower 2 kBytes of external data memory.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 37 of 88

CFG841 ADuC841 Config SFR

SFR Address AFH

Power-On Default 10H1

Bit Addressable No

Table 14. CFG841 SFR Bit Designations

Bit No. Name Description

7 EXSP Extended SP Enable.

When set to 1 by the user, the stack rolls over from SPH/SP = 00FFH to 0100H.

When set to 0 by the user, the stack rolls over from SP = FFH to SP = 00H.

6 PWPO PWM Pin Out Selection.

Set to 1 by the user to select P3.4 and P3.3 as the PWM output pins.

Set to 0 by the user to select P2.6 and P2.7 as the PWM output pins.

5 DBUF DAC Output Buffer.

Set to 1 by the user to bypass the DAC output buffer.

Set to 0 by the user to enable the DAC output buffer.

4 EPM2 Flash/EE Controller and PWM Clock Frequency Configuration Bits.

Frequency should be configured such that FOSC/Divide Factor = 32 kHz + 50%.

EPM1

EPM0

EPM2 EPM1 EPM0 Divide Factor

0 0 0 32

0 0 1 64

0 1 0 128

0 1 1 256

1 0 0 512

1 0 1 1024

1 MSPI Set to 1 by the user to move the SPI functionality of MISO, MOSI, and SCLOCK to P3.3, P3.4, and P3.5,

respectively.

Set to 0 by the user to leave the SPI functionality as usual on MISO, MOSI, and SCLOCK pins.

0 XRAMEN XRAM Enable Bit.

When set to 1 by the user, the internal XRAM is mapped into the lower two kBytes of the external address

space.

When set to 0 by the user, the internal XRAM is not accessible, and the external data memory is mapped into

the lower two kBytes of external data memory.

1 Note that the Flash/EE controller bits EPM2, EPM1, EPM0 are set to their correct values depending on the crystal frequency at power-up. The user should not modify

these bits so all instructions to the CFG841 register should use the ORL, XRL, or ANL instructions. Value of 10H is for 11.0592 MHz crystal.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 38 of 88

USER INTERFACE TO ON-CHIP PERIPHERALS

This section gives a brief overview of the various peripherals

also available on-chip. A summary of the SFRs used to control

and configure these peripherals is also given.

DAC

The ADuC841/ADuC842 incorporate two 12-bit voltage output

DACs on-chip. Each has a rail-to-rail voltage output buffer

capable of driving 10 kΩ/100 pF. Each has two selectable ranges,

0 V to VREF (the internal band gap 2.5 V reference) and 0 V to

AVDD. Each can operate in 12-bit or 8-bit mode.

Both DACs share a control register, DACCON, and four data

registers, DAC1H/L, DAC0/L. Note that in 12-bit asynchronous

mode, the DAC voltage output is updated as soon as the DACL

data SFR has been written; therefore, the DAC data registers

should be updated as DACH first, followed by DACL. Note that

for correct DAC operation on the 0 V to VREF range, the ADC

must be switched on. This results in the DAC using the correct

reference value.

DACCON DAC Control Register

SFR Address FDH

Power-On Default 04H

Bit Addressable No

Table 15. DACCON SFR Bit Designations

Bit No. Name Description

7 MODE The DAC MODE bit sets the overriding operating mode for both DACs.

Set to 1 by the user to select 8-bit mode (write 8 bits to DACxL SFR).

Set to 0 by the user to select 12-bit mode.

6 RNG1 DAC1 Range Select Bit.

Set to 1 by the user to select the range for DAC1 as 0 V to VDD.

Set to 0 by the user to select the range for DAC1 as 0 V to VREF.

5 RNG0 DAC0 Range Select Bit.

Set to 1 by the user to select the range for DAC0 as 0 V to VDD.

Set to 0 by the user to select the range for DAC0 as 0 V to VREF.

4 CLR1 DAC1 Clear Bit.

Set to 1 by the user to leave the output of DAC1 at its normal level.

Set to 0 by the user to force the output of DAC1 to 0 V.

3 CLR0 DAC0 Clear Bit.

Set to 1 by the user to leave the output of DAC0 at its normal level.

Set to 0 by the user to force the output of DAC0 to 0 V.

2 SYNC DAC0/1 Update Synchronization Bit.

When set to 1, the DAC outputs update as soon as DACxL SFRs are written. The user can simultaneously update

both DACs by first updating the DACxL/H SFRs while SYNC is 0. Both DACs then update simultaneously when the

SYNC bit is set to 1.

1 PD1 DAC1 Power-Down Bit.

Set to 1 by the user to power on DAC1.

Set to 0 by the user to power off DAC1.

0 PD0 DAC0 Power-Down Bit.

Set to 1 by the user to power on DAC0.

Set to 0 by the user to power off DAC0.

DACxH/L DAC Data Registers

Function DAC data registers, written by the user to update the DAC output.

SFR Address DAC0L (DAC0 Data Low Byte) -> F9H; DAC1L (DAC1 Data Low Byte) -> FBH

DACH (DAC0 Data High Byte) -> FAH; DAC1H (DAC1 Data High Byte) -> FCH

Power-On Default 00H All Four Registers.

Bit Addressable No All Four Registers.

The 12-bit DAC data should be written into DACxH/L right-justified such that DACxL contains the lower 8 bits, and the lower nibble of

DACxH contains the upper 4 bits.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 39 of 88

Using the DAC

The on-chip DAC architecture consists of a resistor string DAC

followed by an output buffer amplifier, the functional equivalent

of which is illustrated in Figure 42. Details of the actual DAC

architecture can be found in U.S. Patent Number 5969657

(www.uspto.gov). Features of this architecture include inherent

guaranteed monotonicity and excellent differential linearity.

OUTPUT

BUFFER

HIGH Z

DISABLE

(FROM MCU)

DAC0

ADuC841/ADuC842

REF

03260-0-041

Figure 42. Resistor String DAC Functional Equivalent

As shown in Figure 42, the reference source for each DAC is

user selectable in software. It can be either AVDD or VREF. In

0 V-to-AVDD mode, the DAC output transfer function spans

from 0 V to the voltage at the AVDD pin. In 0 V-to-VREF mode,

the DAC output transfer function spans from 0 V to the internal

VREF or, if an external reference is applied, the voltage at the CREF

pin. The DAC output buffer amplifier features a true rail-to-rail

output stage implementation. This means that unloaded, each

output is capable of swinging to within less than 100 mV of

both AVDD and ground. Moreover, the DAC’s linearity specifica-

tion (when driving a 10 kΩ resistive load to ground) is guaranteed

through the full transfer function except Codes 0 to 100, and, in

0 V-to-AVDD mode only, Codes 3995 to 4095. Linearity degrada-

tion near ground and VDD is caused by saturation of the output

amplifier, and a general representation of its effects (neglecting

offset and gain error) is illustrated in Figure 43. The dotted line

in Figure 43 indicates the ideal transfer function, and the solid

line represents what the transfer function might look like with

endpoint nonlinearities due to saturation of the output amplifier.

Note that Figure 43 represents a transfer function in 0 V-to-VDD

mode only. In 0 V-to-VREF mode (with VREF < VDD), the lower

nonlinearity would be similar, but the upper portion of the

transfer function would follow the ideal line right to the end

(VREF in this case, not VDD), showing no signs of endpoint

linearity errors.

–50mV

–100mV

100mV

50mV

0mV 000H FFFH

03260-0-042

Figure 43. Endpoint Nonlinearities Due to Amplifier Saturation

SOURCE/SINK CURRENT (mA)

0 5 10 15

OUTPUT VOLTAGE (V)

DAC LOADED WITH 0000H

DAC LOADED WITH 0FFFH

03260-0-043

Figure 44. Source and Sink Current Capability with VREF = VDD = 5 V

SOURCE/SINK CURRENT (mA)

0 5 10 15

OUTPUT VOLTAGE (V)

DAC LOADED WITH 0000H

DAC LOADED WITH 0FFFH

03260-0-044

Figure 45. Source and Sink Current Capability with VREF = VDD = 3 V

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 40 of 88

The endpoint nonlinearities illustrated in Figure 43 become

worse as a function of output loading. Most of the part’s

specifications assume a 10 kΩ resistive load to ground at the

DAC output. As the output is forced to source or sink more

current, the nonlinear regions at the top or bottom (respectively)

of Figure 43 become larger. Larger current demands can sig-

nificantly limit output voltage swing. Figure 44 and Figure 45

illustrate this behavior. Note that the upper trace in each of

these figures is valid only for an output range selection of

0 V-to-AVDD. In 0 V-to-VREF mode, DAC loading does not cause

high-side voltage drops as long as the reference voltage remains

below the upper trace in the corresponding figure. For example,

if AVDD = 3 V and VREF = 2.5 V, the high-side voltage is not be

affected by loads less than 5 mA. But somewhere around 7 mA,

the upper curve in Figure 45 drops below 2.5 V (VREF), indicating

that at these higher currents the output is not capable of

reaching VREF.

To reduce the effects of the saturation of the output amplifier at

values close to ground and to give reduced offset and gain errors,

the internal buffer can be bypassed. This is done by setting the

DBUF bit in the CFG841/CFG842 register. This allows a full

rail-to-rail output from the DAC, which should then be buffered

externally using a dual-supply op amp in order to get a rail-to-

rail output. This external buffer should be located as close as

physically possible to the DAC output pin on the PCB. Note that

the unbuffered mode works only in the 0 V to VREF range.

To drive significant loads with the DAC outputs, external

buffering may be required (even with the internal buffer

enabled), as illustrated in Figure 46. Table 11 lists some

recommended op amps.

ADuC841/

ADuC842

DAC0

DAC1

03260-0-045

Figure 46. Buffering the DAC Outputs

The DAC output buffer also features a high impedance disable

function. In the chip’s default power-on state, both DACs are

disabled, and their outputs are in a high impedance state (or

three-state) where they remain inactive until enabled in

software. This means that if a zero output is desired during

power-up or power-down transient conditions, then a pull-

down resistor must be added to each DAC output. Assuming

this resistor is in place, the DAC outputs remain at ground

potential whenever the DAC is disabled.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 41 of 88

ON-CHIP PLL

The ADuC842 and ADuC843 are intended for use with a

32.768 kHz watch crystal. A PLL locks onto a multiple (512) of

this to provide a stable 16.78 MHz clock for the system. The

ADuC841 operates directly from an external crystal. The core

can operate at this frequency or at binary submultiples of it to

allow power saving in cases where maximum core performance

is not required. The default core clock is the PLL clock divided

by 8 or 2.097152 MHz. The ADC clocks are also derived from

the PLL clock, with the modulator rate being the same as the

crystal oscillator frequency. The preceding choice of frequencies

ensures that the modulators and the core are synchronous,

regardless of the core clock rate. The PLL control register is

PLLCON.

At 5 V the core clock can be set to a maximum of 16.78 MHz,

while at 3 V the maximum core clock setting is 8.38 MHz. The

CD bits should not be set to 0 on a 3 V part.

Note that on the ADuC841, changing the CD bits in PLLCON

causes the core speed to change. The core speed is crystal freq/

2CD. The other bits in PLLCON are reserved in the case of the

ADuC841 and should be written with 0.

PLLCON PLL Control Register

SFR Address D7H

Power-On Default 53H

Bit Addressable No

Table 16. PLLCON SFR Bit Designations

Bit No. Name Description

7 OSC_PD Oscillator Power-Down Bit.

Set by the user to halt the 32 kHz oscillator in power-down mode.

Cleared by the user to enable the 32 kHz oscillator in power-down mode.

This feature allows the TIC to continue counting even in power-down mode.

6 LOCK PLL Lock Bit.

This is a read-only bit.

Set automatically at power-on to indicate that the PLL loop is correctly tracking the crystal clock. If the external

crystal subsequently becomes disconnected, the PLL will rail.

Cleared automatically at power-on to indicate that the PLL is not correctly tracking the crystal clock. This may be due

to the absence of a crystal clock or an external crystal at power-on. In this mode, the PLL output can be 16.78 MHz

±20%.

5 ---- Reserved. Should be written with 0.

4 ---- Reserved. Should be written with 0.

3 FINT Fast Interrupt Response Bit.

Set by the user enabling the response to any interrupt to be executed at the fastest core clock frequency, regardless

of the configuration of the CD2–0 bits (see below). Once user code has returned from an interrupt, the core resumes

code execution at the core clock selected by the CD2–0 bits.

Cleared by the user to disable the fast interrupt response feature.

2 CD2 CPU (Core Clock) Divider Bits.

1 CD1 This number determines the frequency at which the microcontroller core operates.

0 CD0 CD2

CD1

CD0

Core Clock Frequency (MHz)

16.777216

8.388608

4.194304

2.097152 (Default Core Clock Frequency)

1.048576

0.524288

0.262144

0.131072

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 42 of 88

PULSE-WIDTH MODULATOR (PWM)

The PWM on the ADuC841/ADuC842/ADuC843 is a highly

flexible PWM offering programmable resolution and an input

clock, and can be configured for any one of six different modes

of operation. Two of these modes allow the PWM to be config-

ured as a ∑-∆ DAC with up to 16 bits of resolution. A block

diagram of the PWM is shown in Figure 47. Note the PWM

clock’s sources are different for the ADuC841, and are given in

Table 17.

CLOCK

SELECT PROGRAMMABLE

DIVIDER

COMPARE

MODE

PWM0H/L PWM1H/L

VCO

TO/EXTERNAL PWM CLOCK

XTAL/15

XTAL

P2.6

P2.7

16-BIT PWM COUNTER

03260-0-046

Figure 47. PWM Block Diagram

The PWM uses five SFRs: the control SFR (PWMCON) and

four data SFRs (PWM0H, PWM0L, PWM1H, and PWM1L).

PWMCON, as described in the following sections, controls the

different modes of operation of the PWM as well as the PWM

clock frequency.

PWM0H/L and PWM1H/L are the data registers that deter-

mine the duty cycles of the PWM outputs. The output pins that

the PWM uses are determined by the CFG841/CFG842 register,

and can be either P2.6 and P2.7 or P3.4 and P3.3. In this section

of the data sheet, it is assumed that P2.6 and P2.7 are selected as

the PWM outputs.

To use the PWM user software, first write to PWMCON to

select the PWM mode of operation and the PWM input clock.

Writing to PWMCON also resets the PWM counter. In any of

the 16-bit modes of operation (Modes 1, 3, 4, 6), user software

should write to the PWM0L or PWM1L SFRs first. This value is

written to a hidden SFR. Writing to the PWM0H or PWM1H

SFRs updates both the PWMxH and the PWMxL SFRs but does

not change the outputs until the end of the PWM cycle in

progress. The values written to these 16-bit registers are then

used in the next PWM cycle.

PWMCON PWM Control SFR

SFR Address AEH

Power-On Default 00H

Bit Addressable No

Table 17. PWMCON SFR Bit Designations

Bit No. Name Description

7 SNGL Turns off PMW output at P2.6 or P3.4, leaving the port pin free for digital I/O.

6 MD2 PWM Mode Bits.

5 MD1 The MD2/1/0 bits choose the PWM mode as follows:

MD2 MD1 MD0 Mode

0 0 0 Mode 0: PWM Disabled

0 0 1 Mode 1: Single variable resolution PWM on P2.7 or P3.3

0 1 0 Mode 2: Twin 8-bit PWM

0 1 1 Mode 3: Twin 16-bit PWM

1 0 0 Mode 4: Dual NRZ 16-bit ∑-∆ DAC

1 0 1 Mode 5: Dual 8-bit PWM

1 1 0 Mode 6: Dual RZ 16-bit ∑-∆ DAC

4 MD0

1 1 1 Reserved

3 CDIV1 PWM Clock Divider.

Scale the clock source for the PWM counter as follows:

CDIV1 CDIV0 Description

0 0 PWM Counter = Selected Clock/1

0 1 PWM Counter = Selected Clock/4

1 0 PWM Counter = Selected Clock/16

2 CDIV0

1 1 PWM Counter = Selected Clock/64

1 CSEL1 PWM Clock Divider.

Select the clock source for the PWM as follows:

CSEL1 CSEL0 Description

0 0 PWM Clock = fXTAL/15, ADuC841 = fOCS/DIVIDE FACTOR /15 (see the CFG841 register)

0 1 PWM Clock = fXTAL, ADuC841 = fOCS/DIVIDE FACTOR (see the CFG841 register)

1 0 PWM Clock = External input at P3.4/T0

0 CSEL0

1 1 PWM Clock = fVCO = 16.777216 MHz, ADuC841 = fOSC

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 43 of 88

PWM Modes of Operation

Mode 0: PWM Disabled

The PWM is disabled allowing P2.6 and P2.7 to be used as

normal.

Mode 1: Single Variable Resolution PWM

In Mode 1, both the pulse length and the cycle time (period) are

programmable in user code, allowing the resolution of the

PWM to be variable.

PWM1H/L sets the period of the output waveform. Reducing

PWM1H/L reduces the resolution of the PWM output but

increases the maximum output rate of the PWM. For example,

setting PWM1H/L to 65536 gives a 16-bit PWM with a maxi-

mum output rate of 266 Hz (16.777 MHz/65536). Setting

PWM1H/L to 4096 gives a 12-bit PWM with a maximum

output rate of 4096 Hz (16.777 MHz/4096).

PWM0H/L sets the duty cycle of the PWM output waveform, as

shown in Figure 48.

P2.7

PWM COUNTER

PWM1H/L

PWM0H/L

03260-0-047

Figure 48. PWM in Mode 1

Mode 2: Twin 8-Bit PWM

In Mode 2, the duty cycle of the PWM outputs and the resolu-

tion of the PWM outputs are both programmable. The maximum

resolution of the PWM output is 8 bits.

PWM1L sets the period for both PWM outputs. Typically, this is

set to 255 (FFH) to give an 8-bit PWM, although it is possible to

reduce this as necessary. A value of 100 could be loaded here to

give a percentage PWM, i.e., the PWM is accurate to 1%.

The outputs of the PWM at P2.6 and P2.7 are shown in Figure 49.

As can be seen, the output of PWM0 (P2.6) goes low when the

PWM counter equals PWM0L. The output of PWM1 (P2.7)

goes high when the PWM counter equals PWM1H and goes

low again when the PWM counter equals PWM0H. Setting

PWM1H to 0 ensures that both PWM outputs start simultaneously.

P2.7

P2.6

PWM COUNTER

PWM1H

PWM1L

PWM0H

PWM0L

03260-0-048

Figure 49. PWM Mode 2

Mode 3: Twin 16-Bit PWM

In Mode 3, the PWM counter is fixed to count from 0 to 65536,

giving a fixed 16-bit PWM. Operating from the 16.777 MHz

core clock results in a PWM output rate of 256 Hz. The duty

cycle of the PWM outputs at P2.6 and P2.7 is independently

programmable.

As shown in Figure 50, while the PWM counter is less than

PWM0H/L, the output of PWM0 (P2.6) is high. Once the PWM

counter equals PWM0H/L, PWM0 (P2.6) goes low and remains

low until the PWM counter rolls over.

Similarly, while the PWM counter is less than PWM1H/L, the

output of PWM1 (P2.7) is high. Once the PWM counter equals

PWM1H/L, PWM1 (P2.7) goes low and remains low until the

PWM counter rolls over.

In this mode, both PWM outputs are synchronized, i.e., once

the PWM counter rolls over to 0, both PWM0 (P2.6) and

PWM1 go high.

P2.7

P2.6

PWM COUNTER

PWM1H/L

65536

PWM0H/L

03260-0-049

Figure 50. PWM Mode 3

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 44 of 88

Mode 4: Dual NRZ 16-Bit ∑-∆ DAC

Mode 4 provides a high speed PWM output similar to that of a

∑-∆ DAC. Typically, this mode is used with the PWM clock

equal to 16.777216 MHz. In this mode, P2.6 and P2.7 are

updated every PWM clock (60 ns in the case of 16 MHz). Over

any 65536 cycles (16-bit PWM) PWM0 (P2.6) is high for

PWM0H/L cycles and low for (65536 – PWM0H/L) cycles.

Similarly, PWM1 (P2.7) is high for PWM1H/L cycles and low

for (65536 – PWM1H/L) cycles.

For example, if PWM1H is set to 4010H (slightly above one

quarter of FS), then typically P2.7 will be low for three clocks

and high for one clock (each clock is approximately 60 ns). Over

every 65536 clocks, the PWM compensates for the fact that the

output should be slightly above one quarter of full scale by

having a high cycle followed by only two low cycles.

16.777MHz

16-BIT

16-BIT 16-BIT

16-BIT

CARRY OUT AT P1.0

CARRY OUT AT P2.7

PWM0H/L = C000H

PWM1H/L = 4000H

001000

LATCH

0111 11

03260-0-050

Figure 51. PWM Mode 4

For faster DAC outputs (at lower resolution), write 0s to the

LSBs that are not required. If, for example, only 12-bit perform-

ance is required, write 0s to the four LSBs. This means that a 12-bit

accurate ∑-∆ DAC output can occur at 4.096 kHz. Similarly

writing 0s to the 8 LSBs gives an 8-bit accurate ∑-∆ DAC output

at 65 kHz.

Mode 5: Dual 8-Bit PWM

In Mode 5, the duty cycle of the PWM outputs and the resolu-

tion of the PWM outputs are individually programmable. The

maximum resolution of the PWM output is 8 bits. The output

resolution is set by the PWM1L and PWM1H SFRs for the P2.6

and P2.7 outputs, respectively. PWM0L and PWM0H sets the

duty cycles of the PWM outputs at P2.6 and P2.7, respectively.

Both PWMs have the same clock source and clock divider.

P2.7

P2.6

PWM COUNTERS

PWM1H

PWM1L

PWM0H

PWM0L

03260-0-051

Figure 52. PWM Mode 5

Mode 6: Dual RZ 16-Bit ∑-∆ DAC

Mode 6 provides a high speed PWM output similar to that of a

∑-∆ DAC. Mode 6 operates very similarly to Mode 4. However,

the key difference is that Mode 6 provides return-to-zero (RZ)

∑-∆ DAC output. Mode 4 provides non-return-to-zero ∑-∆

DAC outputs. The RZ mode ensures that any difference in the

rise and fall times will not affect the ∑-∆ DAC INL. However,

the RZ mode halves the dynamic range of the ∑-∆ DAC outputs

from 0 V–AVDD down to 0 V–AVDD/2. For best results, this mode

should be used with a PWM clock divider of 4.

If PWM1H is set to 4010H (slightly above one quarter of FS),

typically P2.7 will be low for three full clocks (3 × 60 ns), high

for half a clock (30 ns), and then low again for half a clock

(30 ns) before repeating itself. Over every 65536 clocks, the

PWM will compensate for the fact that the output should be

slightly above one quarter of full scale by leaving the output

high for two half clocks in four. The rate at which this happens

depends on the value and degree of compensation required.

4MHz

16-BIT

240

16-BIT 16-BIT

16-BIT

CARRY OUT AT P2.6

CARRY OUT AT P2.7

PWM0H/L = C000H

PWM1H/L = 4000H

1000

LATCH

0111 11

240

0, 3/4, 1/2, 1/4, 0

03260-0-052

Figure 53. PWM Mode 6

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 45 of 88

SERIAL PERIPHERAL INTERFACE (SPI)

The ADuC841/ADuC842/ADuC843 integrate a complete hard-

ware serial peripheral interface on-chip. SPI is an industry-

standard synchronous serial interface that allows 8 bits of data

to be synchronously transmitted and received simultaneously,

i.e., full duplex. Note that the SPI pins are shared with the I2C

pins. Therefore, the user can enable only one interface or the

other on these pins at any given time (see SPE in Table 18). SPI

can be operated at the same time as the I2C interface if the

MSPI bit in CFG841/CFG8842 is set. This moves the SPI

outputs (MISO, MOSI, and SCLOCK) to P3.3, P3.4, and P3.5,

respectively). The SPI port can be configured for master or slave

operation and typically consists of four pins, described in the

following sections.

MISO (Master In, Slave Out Data I/O Pin)

The MISO pin is configured as an input line in master mode

and as an output line in slave mode. The MISO line on the

master (data in) should be connected to the MISO line in the

slave device (data out). The data is transferred as byte-wide

(8-bit) serial data, MSB first.

MOSI (Master Out, Slave In Pin)

The MOSI pin is configured as an output line in master mode

and as an input line in slave mode. The MOSI line on the master

(data out) should be connected to the MOSI line in the slave

device (data in). The data is transferred as byte-wide (8-bit)

serial data, MSB first.

SCLOCK (Serial Clock I/O Pin)

The master serial clock (SCLOCK) is used to synchronize the

data being transmitted and received through the MOSI and

MISO data lines. A single data bit is transmitted and received in

each SCLOCK period. Therefore, a byte is transmitted/received

after eight SCLOCK periods. The SCLOCK pin is configured as

an output in master mode and as an input in slave mode. In

master mode, the bit rate, polarity, and phase of the clock are

controlled by the CPOL, CPHA, SPR0, and SPR1 bits in the

SPICON SFR (see Table 18). In slave mode, the SPICON register

must be configured with the phase and polarity (CPHA and

CPOL) of the expected input clock. In both master and slave

modes, the data is transmitted on one edge of the SCLOCK

signal and sampled on the other. It is important, therefore, that

CPHA and CPOL are configured the same for the master and

slave devices.

SS (Slave Select Input Pin)

The SS pin is shared with the ADC5 input. To configure this pin

as a digital input, the bit must be cleared, e.g., CLR P1.5. This

line is active low. Data is received or transmitted in slave mode

only when the SS pin is low, allowing the parts to be used in

single-master, multislave SPI configurations. If CPHA = 1, the

SS input may be permanently pulled low. If CPHA = 0, the SS

input must be driven low before the first bit in a byte-wide

transmission or reception and return high again after the last bit

in that byte-wide transmission or reception. In SPI slave mode,

the logic level on the external SS pin can be read via the SPR0

bit in the SPICON SFR. The SFR registers, described in the

following tables, are used to control the SPI interface.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 46 of 88

SPICON SPI Control Register

SFR Address F8H

Power-On Default 04H

Bit Addressable Yes

Table 18. SPICON SFR Bit Designations

Bit No. Name Description

7 ISPI SPI Interrupt Bit.

Set by the MicroConverter at the end of each SPI transfer.

Cleared directly by user code or indirectly by reading the SPIDAT SFR.

6 WCOL Write Collision Error Bit.

Set by the MicroConverter if SPIDAT is written to while an SPI transfer is in progress.

Cleared by user code.

5 SPE SPI Interface Enable Bit.

Set by the user to enable the SPI interface.

Cleared by the user to enable the I2C pins, this is not requiredto enable the I2C interface if the MSPI bit is set in

CFG841/CFG842. In this case, the I2C interface is automatically enabled.

4 SPIM SPI Master/Slave Mode Select Bit.

Set by the user to enable master mode operation (SCLOCK is an output).

Cleared by the user to enable slave mode operation (SCLOCK is an input).

3 CPOL1 Clock Polarity Select Bit.

Set by the user if SCLOCK idles high.

Cleared by the user if SCLOCK idles low.

2 CPHA1 Clock Phase Select Bit.

Set by the user if leading SCLOCK edge is to transmit data.

Cleared by the user if trailing SCLOCK edge is to transmit data.

1 SPR1 SPI Bit Rate Select Bits.

0 SPR0 These bits select the SCLOCK rate (bit rate) in master mode as follows:

SPR1 SPR0 Selected Bit Rate

0 0 fOSC/2

0 1 fOSC/4

1 0 fOSC/8

1 1 fOSC/16

In SPI slave mode, i.e., SPIM = 0, the logic level on the external SS pin can be read via the SPR0 bit.

1The CPOL and CPHA bits should both contain the same values for master and slave devices.

SPIDAT SPI Data Register

Function SPIDAT SFR is written by the user to transmit data over the SPI interface or read by user code to

read data just received by the SPI interface.

SFR Address F7H

Power-On Default 00H

Bit Addressable No

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 47 of 88

Using the SPI Interface

Depending on the configuration of the bits in the SPICON SFR

shown in Table 18, the ADuC841/ADuC842/ADuC843 SPI

interface transmits or receives data in a number of possible

modes. Figure 54 shows all possible SPI configurations for the

parts, and the timing relationships and synchronization

between the signals involved. Also shown in this figure is the

SPI interrupt bit (ISPI) and how it is triggered at the end of each

byte-wide communication.

SCLOCK

(CPOL = 1)

SCLOCK

(CPOL = 0)

(CPHA = 1)

(CPHA = 0)

SAMPLE INPUT

ISPI FLAG

DATA OUTPUT

ISPI FLAG

SAMPLE INPUT

DATA OUTPUT

MSB BIT 6 BIT 5 ?

BIT 4 BIT 3 BIT 2 BIT 1 LSB

MSB BIT 6 BIT 5 BIT 4 BIT 3 BIT 2 BIT 1 LSB

03260-0-053

Figure 54. SPI Timing, All Modes

SPI Interface—Master Mode

In master mode, the SCLOCK pin is always an output and

generates a burst of eight clocks whenever user code writes to

the SPIDAT register. The SCLOCK bit rate is determined by

SPR0 and SPR1 in SPICON. Also note that the SS pin is not

used in master mode. If the parts need to assert the SS pin on an

external slave device, a port digital output pin should be used.

In master mode, a byte transmission or reception is initiated by

a write to SPIDAT. Eight clock periods are generated via the

SCLOCK pin and the SPIDAT byte being transmitted via MOSI.

With each SCLOCK period, a data bit is also sampled via MISO.

After eight clocks, the transmitted byte will be completely

transmitted, and the input byte will be waiting in the input shift

will occur if enabled. The value in the shift register will be

latched into SPIDAT.

SPI Interface—Slave Mode

In slave mode, SCLOCK is an input. The SS pin must also be

driven low externally during the byte communication. Trans-

mission is also initiated by a write to SPIDAT. In slave mode, a

data bit is transmitted via MISO, and a data bit is received via

MOSI through each input SCLOCK period. After eight clocks,

the transmitted byte will be completely transmitted, and the

input byte will be waiting in the input shift register. The ISPI

flag will be set automatically, and an interrupt will occur if

enabled. The value in the shift register will be latched into

SPIDAT only when the transmission/reception of a byte has

been completed. The end of transmission occurs after the

eighth clock has been received if CPHA = 1, or when SS returns

high if CPHA = 0.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 48 of 88

I2C COMPATIBLE INTERFACE

The ADuC841/ADuC842/ADuC843 support a fully licensed

I2C serial interface. The I2C interface is implemented as a full

hardware slave and software master. SDATA is the data I/O pin,

and SCLOCK is the serial clock. These two pins are shared with

the MOSI and SCLOCK pins of the on-chip SPI interface. To

enable the I2C interface, the SPI interface must be turned off

(see SPE in Table 18) or the SPI interface must be moved to

P3.3, P3.4, and P3.5 via the CFG841.1/CFG842.1 bit. Application

Note uC001 describes the operation of this interface as imple-

mented and is available from the MicroConverter website at

www.analog.com/microconverter.

Three SFRs are used to control the I2C interface and are

described in the following tables.

I2CCON I2C Control Register

SFR Address E8H

Power-On Default 00H

Bit Addressable Yes

Table 19. I2CCON SFR Bit Designations, Master Mode

Bit No. Name Description

7 MDO I2C Software Master Data Output Bit (Master Mode Only).

This data bit is used to implement a master I2C transmitter interface in software. Data written to this bit is output on

the SDATA pin if the data output enable (MDE) bit is set.

6 MDE I2C Software Master Data Output Enable Bit (Master Mode Only).

Set by the user to enable the SDATA pin as an output (Tx).

Cleared by the user to enable the SDATA pin as an input (Rx).

5 MCO I2C Software Master Clock Output Bit (Master Mode Only).

This data bit is used to implement a master I2C transmitter interface in software. Data written to this bit is output on

the SCLOCK pin.

4 MDI I2C Software Master Data Input Bit (Master Mode Only).

This data bit is used to implement a master I2C receiver interface in software. Data on the SDATA pin is latched into

this bit on SCLOCK if the data output enable (MDE) bit is 0.

3 I2CM I2C Master/Slave Mode Bit.

Set by the user to enable I2C software master mode.

Cleared by the user to enable I2C hardware slave mode.

2 ---- Reserved.

1 ---- Reserved.

0 ---- Reserved.

Table 20. I2CCON SFR Bit Designations, Slave Mode

Bit No. Name Description

7 I2CSI I2C Stop Interrupt Enable Bit.

Set by the user to enable I2C stop interrupts. If set, a stop bit that follows a valid start condition generates an

interrupt.

Cleared by the user to disable I2C stop interrupts.

6 I2CGC I2C General Call Status Bit.

Set by hardware after receiving a general call address.

Cleared by the user.

5 I2CID1 I2C Interrupt Decode Bits.

4 I2CID0 Set by hardware to indicate the source of an I2C interrupt.

00 Start and Matching Address.

01 Repeated Start and Matching Address.

10 User Data.

11 Stop after a Start and Matching Address.

3 I2CM I2C Master/Slave Mode Bit.

Set by the user to enable I2C software master mode.

Cleared by the user to enable I2C hardware slave mode.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 49 of 88

Bit No. Name Description

2 I2CRS I2C Reset Bit (Slave Mode Only).

Set by the user to reset the I2C interface.

Cleared by the user code for normal I2C operation.

1 I2CTX I2C Direction Transfer Bit (Slave Mode Only).

Set by the MicroConverter if the interface is transmitting.

Cleared by the MicroConverter if the interface is receiving.

0 I2CI I2C Interrupt Bit (Slave Mode Only).

Set by the MicroConverter after a byte has been transmitted or received.

Cleared automatically when user code reads the I2CDAT SFR (see I2CDAT below).

I2CADD I2C Address Register

Function Holds the first I2C peripheral address for the part. It may be overwritten by user code. Application Note

uC001 at www.analog.com/microconverter describes the format of the I2C standard 7-bit address in

detail.

SFR Address 9BH

Power-On Default 55H

Bit Addressable No

I2CADD1 I2C Address Register

Function Holds the second I2C peripheral address for the part. It may be overwritten by user code.

SFR Address 91H

Power-On Default 7FH

Bit Addressable No

I2CADD2 I2C Address Register

Function Holds the third I2C peripheral address for the part. It may be overwritten by user code.

SFR Address 92H

Power-On Default 7FH

Bit Addressable No

I2CADD3 I2C Address Register

Function Holds the fourth I2C peripheral address for the part. It may be overwritten by user code.

SFR Address 93H

Power-On Default 7FH

Bit Addressable No

I2CDAT I2C Data Register

Function Written by the user to transmit data over the I2C interface or read by user code to read data just

received by the I2C interface. Accessing I2CDAT automatically clears any pending I2C interrupt and

the I2CI bit in the I2CCON SFR. User software should access I2CDAT only once per interrupt cycle.

SFR Address 9AH

Power-On Default 00H

Bit Addressable No

The main features of the MicroConverter I2C interface are

• Only two bus lines are required: a serial data line (SDATA)

and a serial clock line (SCLOCK).

• An I2C master can communicate with multiple slave

devices. Because each slave device has a unique 7-bit

address, single master/slave relationships can exist at all

times even in a multislave environment.

• Ability to respond to four separate addresses when

operating in slave mode.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 50 of 88

• An I2C slave can respond to repeated start conditions

without a stop bit in between. This allows a master to

change direction of transfer without giving up the bus.

Note that the repeated start is detected only when a slave

has previously been configured as a receiver.

• On-chip filtering rejects <50 ns spikes on the SDATA and

the SCLOCK lines to preserve data integrity.

MASTER I

SLAVE 1

SLAVE 2

03260-0-054

Figure 55. Typical I2C System

Software Master Mode

The ADuC841/ADuC842/ADuC843 can be used as I2C master

devices by configuring the I2C peripheral in master mode and

writing software to output the data bit by bit. This is referred to

as a software master. Master mode is enabled by setting the I2CM

bit in the I2CCON register.

To transmit data on the SDATA line, MDE must be set to enable

the output driver on the SDATA pin. If MDE is set, the SDATA

pin is pulled high or low depending on whether the MDO bit is

set or cleared. MCO controls the SCLOCK pin and is always

configured as an output in master mode. In master mode, the

SCLOCK pin is pulled high or low depending on the whether

MCO is set or cleared.

To receive data, MDE must be cleared to disable the output

driver on SDATA. Software must provide the clocks by toggling

the MCO bit and reading the SDATA pin via the MDI bit. If

MDE is cleared, MDI can be used to read the SDATA pin. The

value of the SDATA pin is latched into MDI on a rising edge of

SCLOCK. MDI is set if the SDATA pin was high on the last

rising edge of SCLOCK. MDI is clear if the SDATA pin was low

on the last rising edge of SCLOCK.

Software must control MDO, MCO, and MDE appropriately to

generate the start condition, slave address, acknowledge bits,

data bytes, and stop conditions. These functions are described

in Application Note uC001.

Hardware Slave Mode

After reset, the ADuC841/ADuC842/ADuC843 default to

hardware slave mode. The I2C interface is enabled by clearing

the SPE bit in SPICON (this is not necessary if the MSPI bit is

set). Slave mode is enabled by clearing the I2CM bit in I2CCON.

The parts have a full hardware slave. In slave mode, the I2C

address is stored in the I2CADD register. Data received or to be

transmitted is stored in the I2CDAT register.

Once enabled in I2C slave mode, the slave controller waits for a

start condition. If the part detects a valid start condition, fol-

lowed by a valid address, followed by the R/W bit, the I2CI

interrupt bit is automatically set by hardware. The I2C peripheral

generates a core interrupt only if the user has pre-configured

the I2C interrupt enable bit in the IEIP2 SFR as well as the

global interrupt bit, EA, in the IE SFR. i.e.,

;Enabling I2C Interrupts for the ADuC842

MOV IEIP2,#01h ; enable I2C interrupt

SETB EA

An autoclear of the I2CI bit is implemented on the parts so that

this bit is cleared automatically on a read or write access to the

I2CDAT SFR.

MOV I2CDAT, A ; I2CI auto-cleared

MOV A, I2CDAT ; I2CI auto-cleared

If for any reason the user tries to clear the interrupt more than

once, i.e., access the data SFR more than once per interrupt, then

the I2C controller will halt. The interface will then have to be

reset using the I2CRS bit.

The user can choose to poll the I2CI bit or to enable the inter-

rupt. In the case of the interrupt, the PC counter vectors to

003BH at the end of each complete byte. For the first byte, when

the user gets to the I2CI ISR, the 7-bit address and the R/W bit

appear in the I2CDAT SFR.

The I2CTX bit contains the R/W bit sent from the master. If

I2CTX is set, the master is ready to receive a byte. Therefore the

slave will transmit data by writing to the I2CDAT register. If

I2CTX is cleared, the master is ready to transmit a byte. There-

fore the slave will receive a serial byte. Software can interrogate

the state of I2CTX to determine whether it should write to or

read from I2CDAT.

Once the part has received a valid address, hardware holds

SCLOCK low until the I2CI bit is cleared by software. This

allows the master to wait for the slave to be ready before

transmitting the clocks for the next byte.

The I2CI interrupt bit is set every time a complete data byte is

received or transmitted, provided it is followed by a valid ACK.

If the byte is followed by a NACK, an interrupt is not generated.

The part continues to issue interrupts for each complete data

byte transferred until a stop condition is received or the inter-

face is reset.

When a stop condition is received, the interface resets to a state

in which it is waiting to be addressed (idle). Similarly, if the

interface receives a NACK at the end of a sequence, it also

returns to the default idle state. The I2CRS bit can be used to

reset the I2C interface. This bit can be used to force the interface

back to the default idle state.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 51 of 88

DUAL DATA POINTER

The ADuC841/ADuC842/ADuC843 incorporate two data

pointers. The second data pointer is a shadow data pointer and

is selected via the data pointer control SFR (DPCON). DPCON

also includes some useful features such as automatic hardware

post-increment and post-decrement as well as automatic data

pointer toggle. DPCON is described in Table 21.

DPCON Data Pointer Control SFR

SFR Address A7H

Power-On Default 00H

Bit Addressable No

Table 21. DPCON SFR Bit Designations

Bit No. Name Description

7 ---- Reserved.

6 DPT Data Pointer Automatic Toggle Enable.

Cleared by the user to disable autoswapping of the DPTR.

Set in user software to enable automatic toggling of the DPTR after each each MOVX or MOVC instruction.

5 DP1m1 Shadow Data Pointer Mode.

These two bits enable extra modes of the shadow data pointer’s operation, allowing for more compact and more

efficient code size and execution.

m1 m0 Behavior of the shadow data pointer.

0 0 8052 behavior.

0 1 DPTR is post-incremented after a MOVX or a MOVC instruction.

1 0 DPTR is post-decremented after a MOVX or MOVC instruction.

4 DP1m0

1 1 DPTR LSB is toggled after a MOVX or MOVC instruction. (This instruction can be useful for moving

8-bit blocks to/from 16-bit devices.)

3 DP0m1 Main Data Pointer Mode.

These two bits enable extra modes of the main data pointer operation, allowing for more compact and more efficient

code size and execution.

m1 m0 Behavior of the main data pointer.

0 0 8052 behavior.

0 1 DPTR is post-incremented after a MOVX or a MOVC instruction.

1 0 DPTR is post-decremented after a MOVX or MOVC instruction.

1 1 DPTR LSB is toggled after a MOVX or MOVC instruction.

2 DP0m0

(This instruction can be useful for moving 8-bit blocks to/from 16-bit devices.)

1 ----

This bit is not implemented to allow the INC DPCON instruction toggle the data pointer without incrementing the rest

of the SFR.

0 DPSEL Data Pointer Select.

Cleared by the user to select the main data pointer. This means that the contents of this 24-bit register are placed into

the three SFRs: DPL, DPH, and DPP.

Set by the user to select the shadow data pointer. This means that the contents of a separate 24-bit register appears in

the three SFRs: DPL, DPH, and DPP.

Note 1: This is the only place where the main and shadow data

pointers are distinguished. Everywhere else in this data sheet

wherever the DPTR is mentioned, operation on the active

DPTR is implied.

Note 2: Only MOVC/MOVX @DPTR instructions are relevant

above. MOVC/MOVX PC/@Ri instructions do not cause the

DPTR to automatically post increment/decrement, and so on.

To illustrate the operation of DPCON, the following code copies

256 bytes of code memory at address D000H into XRAM

starting from Address 0000H.

MOV DPTR,#0 ; Main DPTR = 0

MOV DPCON,#55H ; Select shadow DPTR

; DPTR1 increment mode,

; DPTR0 increment mode

; DPTR auto toggling ON

MOV DPTR,#0D000H ; Shadow DPTR = D000H

MOVELOOP:

CLR A

MOVC A,@A+DPTR ; Get data

; Post Inc DPTR

; Swap to Main DPTR (Data)

MOVX @DPTR,A ; Put ACC in XRAM

; Increment main DPTR

; Swap Shadow DPTR (Code)

MOV A, DPL

JNZ MOVELOOP

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 52 of 88

POWER SUPPLY MONITOR

As its name suggests, the power supply monitor, once enabled,

monitors the DVDD supply on the ADuC841/ADuC842/

ADuC843. It indicates when any of the supply pins drops below

one of two user selectable voltage trip points, 2.93 V and 3.08 V.

For correct operation of the power supply monitor function,

AVDD must be equal to or greater than 2.7 V. Monitor function is

controlled via the PSMCON SFR. If enabled via the IEIP2 SFR,

the monitor interrupts the core using the PSMI bit in the

PSMCON SFR. This bit is not cleared until the failing power

supply has returned above the trip point for at least 250 ms.

This monitor function allows the user to save working registers

to avoid possible data loss due to the low supply condition, and

also ensures that normal code execution does not resume until a

safe supply level has been well established. The supply monitor

is also protected against spurious glitches triggering the

interrupt circuit.

Note that the 5 V part has an internal POR trip level of 4.5 V,

which means that there are no usable PSM levels on the 5 V

part. The 3 V part has a POR trip level of 2.45 V, allowing all

PSM trip points to be used.

PSMCON

Power Supply Monitor

Control Register

SFR Address DFH

Power-On Default DEH

Bit Addressable No

Table 22. PSMCON SFR Bit Designations

Bit No. Name Description

7 ---- Reserved.

6 CMPD DVDD Comparator Bit.

This is a read-only bit that directly reflects the state of the DVDD comparator.

Read 1 indicates that the DVDD supply is above its selected trip point.

Read 0 indicates that the DVDD supply is below its selected trip point.

5 PSMI Power Supply Monitor Interrupt Bit.

This bit is set high by the MicroConverter if either CMPA or CMPD is low, indicating low analog or digital supply. The

PSMI bit can be used to interrupt the processor. Once CMPD and/or CMPA return (and remain) high, a 250 ms

counter is started. When this counter times out, the PSMI interrupt is cleared. PSMI can also be written by the user.

However, if either comparator output is low, it is not possible for the user to clear PSMI.

4 TPD1 DVDD Trip Point Selection Bits.

These bits select the DVDD trip point voltage as follows:

TPD1 TPD0 Selected DVDD Trip Point (V)

0 0 Reserved

0 1 3.08

1 0 2.93

3 TPD0

1 1 Reserved

2 ---- Reserved.

1 ---- Reserved.

0 PSMEN Power Supply Monitor Enable Bit.

Set to 1 by the user to enable the power supply monitor circuit.

Cleared to 0 by the user to disable the power supply monitor circuit.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 53 of 88

WATCHDOG TIMER

The purpose of the watchdog timer is to generate a device reset

or interrupt within a reasonable amount of time if the ADuC841/

ADuC842/ADuC843 enter an erroneous state, possibly due to a

programming error or electrical noise. The watchdog function

can be disabled by clearing the WDE (watchdog enable) bit in

the watchdog control (WDCON) SFR. When enabled, the

watchdog circuit generates a system reset or interrupt (WDS) if

the user program fails to set the watchdog (WDE) bit within a

predetermined amount of time (see PRE3-0 bits in Table 23.

The watchdog timer is clocked directly from the 32 kHz

external crystal on the ADuC842/ADuC843. On the ADuC841,

the watchdog timer is clocked by an internal R/C oscillator at

32 kHz ±10%. The WDCON SFR can be written only by user

software if the double write sequence described in WDWR

below is initiated on every write access to the WDCON SFR.

WDCON Watchdog Timer Control Register

SFR Address C0H

Power-On Default 10H

Bit Addressable Yes

Table 23. WDCON SFR Bit Designations

Bit No. Name Description

7 PRE3 Watchdog Timer Prescale Bits.

6 PRE2

The watchdog timeout period is given by the equation

tWD = (2PRE × (29/ fXTAL))

5 PRE1 (0 – PRE – 7; fXTAL = 32.768 kHz (ADuC842/ADuC843), or 32kHz ± 10%(ADuC841) )

PRE3 PRE2 PRE1 PRE0 Timeout Period (ms) Action

0 0 0 0 15.6 Reset or Interrupt

0 0 0 1 31.2 Reset or Interrupt

0 0 1 0 62.5 Reset or Interrupt

0 0 1 1 125 Reset or Interrupt

0 1 0 0 250 Reset or Interrupt

0 1 0 1 500 Reset or Interrupt

0 1 1 0 1000 Reset or Interrupt

0 1 1 1 2000 Reset or Interrupt

1 0 0 0 0.0 Immediate Reset

4 PRE0

PRE3–0 > 1000 Reserved

3 WDIR Watchdog Interrupt Response Enable Bit.

If this bit is set by the user, the watchdog generates an interrupt response instead of a system reset when the

watchdog timeout period has expired. This interrupt is not disabled by the CLR EA instruction, and it is also a fixed,

high priority interrupt. If the watchdog is not being used to monitor the system, it can be used alternatively as a

timer. The prescaler is used to set the timeout period in which an interrupt will be generated.

2 WDS Watchdog Status Bit.

Set by the watchdog controller to indicate that a watchdog timeout has occurred.

Cleared by writing a 0 or by an external hardware reset. It is not cleared by a watchdog reset.

1 WDE Watchdog Enable Bit.

Set by the user to enable the watchdog and clear its counters. If this bit is not set by the user within the watchdog

timeout period, the watchdog generates a reset or interrupt, depending on WDIR.

Cleared under the following conditions: user writes 0, watchdog reset (WDIR = 0); hardware reset; PSM interrupt.

Watchdog Write Enable Bit.

To write data to the WDCON SFR involves a double instruction sequence. The WDWR bit must be set and the very

next instruction must be a write instruction to the WDCON SFR.

For example:

CLR EA ;disable interrupts while writing

;to WDT

SETB WDWR ;allow write to WDCON

MOV WDCON,#72H ;enable WDT for 2.0s timeout

0 WDWR

SETB EA ;enable interrupts again (if rqd)

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 54 of 88

TIME INTERVAL COUNTER (TIC)

A TIC is provided on-chip for counting longer intervals than

the standard 8051 compatible timers are capable of. The TIC is

capable of timeout intervals ranging from 1/128 second to 255

hours. Furthermore, this counter is clocked by the external

32.768 kHz crystal rather than by the core clock, and it has the

ability to remain active in power-down mode and time long

power-down intervals. This has obvious applications for remote

battery-powered sensors where regular widely spaced readings

are required.

Six SFRs are associated with the time interval counter, TIMECON

being its control register. Depending on the configuration of the

IT0 and IT1 bits in TIMECON, the selected time counter regis-

ter overflow clocks the interval counter. When this counter is

equal to the time interval value loaded in the INTVAL SFR, the

TII bit (TIMECON.2) is set and generates an interrupt if enabled.

If the part is in power-down mode, again with TIC interrupt

enabled, the TII bit wakes up the device and resumes code

execution by vectoring directly to the TIC interrupt service

vector address at 0053H. The TIC-related SFRs are described in

Table 24. Note also that the time based SFRs can be written

initially with the current time; the TIC can then be controlled

and accessed by user software. In effect, this facilitates the

implementation of a real-time clock. A block diagram of the

TIC is shown in Figure 56.

The TIC is clocked directly from a 32 kHz external crystal on

the ADuC842/ADuC843 and by the internal 32 kHz ±10% R/C

oscillator on the ADuC841. Due to this, instructions that access

the TIC registers will also be clocked at this speed. The user

should ensure that there is sufficient time between instructions

to these registers to allow them to execute correctly.

8-BIT

PRESCALER

HUNDREDTHS COUNTER

HTHSEC

SECOND COUNTER

SEC

MINUTE COUNTER

MIN

HOUR COUNTER

HOUR

TIEN

INTERVAL TIMEOUT

IME INTERVAL COUNTER INTERRUPT

8-BIT

INTERVAL COUNTER

TIMER INTVAL

INTVAL

INTERVAL

TIMEBASE

SELECTION

MUX

TCEN 32.768kHz EXTERNAL CRYSTAL

ITS0, 1

COMPARE

COUNT = INTVAL

03260-0-055

Figure 56. TIC, Simplified Block Diagram

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 55 of 88

Table 24. TIMECON SFR Bit Designations

Bit No. Name Description

7 ---- Reserved.

6 TFH

Twenty-Four Hour Select Bit.

Set by the user to enable the hour counter to count from 0 to 23.

Cleared by the user to enable the hour counter to count from 0 to 255.

5 ITS1 Interval Timebase Selection Bits.

4 ITS0 Written by user to determine the interval counter update rate.

ITS1 ITS0 Interval Timebase

0 0 1/128 Second

0 1 Seconds

1 0 Minutes

1 1 Hours

3 STI

Single Time Interval Bit.

Set by the user to generate a single interval timeout. If set, a timeout clears the TIEN bit.

Cleared by the user to allow the interval counter to be automatically reloaded and start counting again at each

interval timeout.

2 TII

TIC Interrupt Bit.

Set when the 8-bit interval counter matches the value in the INTVAL SFR.

Cleared by user software.

1 TIEN

Time Interval Enable Bit.

Set by the user to enable the 8-bit time interval counter.

Cleared by the user to disable the interval counter.

0 TCEN

Time Clock Enable Bit.

Set by the user to enable the time clock to the time interval counters.

Cleared by the user to disable the clock to the time interval counters and reset the time interval SFRs to the last

value written to them by the user. The time registers (HTHSEC, SEC, MIN, and HOUR) can be written while TCEN

is low.

TIMECON TIC Control Register

SFR Address A1H

Power-On Default 00H

Bit Addressable No

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 56 of 88

INTVAL User Time Interval Select Register

Function User code writes the required time interval to this register. When the 8-bit interval counter is equal to the

time interval value loaded in the INTVAL SFR, the TII bit (TIMECON.2) is set and generates an

interrupt if enabled.

SFR Address A6H

Power-On Default 00H

Bit Addressable No

Valid Value 0 to 255 decimal

HTHSEC Hundredths Seconds Time Register

Function This register is incremented in 1/128 second intervals once TCEN in TIMECON is active. The HTHSEC

SFR counts from 0 to 127 before rolling over to increment the SEC time register.

SFR Address A2H

Power-On Default 00H

Bit Addressable No

Valid Value 0 to 127 decimal

SEC Seconds Time Register

Function This register is incremented in 1-second intervals once TCEN in TIMECON is active. The SEC SFR

counts from 0 to 59 before rolling over to increment the MIN time register.

SFR Address A3H

Power-On Default 00H

Bit Addressable No

Valid Value 0 to 59 decimal

MIN Minutes Time Register

Function This register is incremented in 1-minute intervals once TCEN in TIMECON is active. The MIN SFR

counts from 0 to 59 before rolling over to increment the HOUR time register.

SFR Address A4H

Power-On Default 00H

Bit Addressable No

Valid Value 0 to 59 decimal

HOUR Hours Time Register

Function This register is incremented in 1-hour intervals once TCEN in TIMECON is active. The HOUR SFR

counts from 0 to 23 before rolling over to 0.

SFR Address A5H

Power-On Default 00H

Bit Addressable No

Valid Value 0 to 23 decimal

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 57 of 88

8052 COMPATIBLE ON-CHIP PERIPHERALS

This section gives a brief overview of the various secondary

peripheral circuits that are also available to the user on-chip.

These remaining functions are mostly 8052 compatible (with a

few additional features) and are controlled via standard 8052

SFR bit definitions.

Parallel I/O

The ADuC841/ADuC842/ADuC843 use four input/output

ports to exchange data with external devices. In addition to

performing general-purpose I/O, some ports are capable of

external memory operations while others are multiplexed with

alternate functions for the peripheral features on the device. In

general, when a peripheral is enabled, that pin may not be used

as a general-purpose I/O pin.

Port 0

Port 0 is an 8-bit open-drain bidirectional I/O port that is

directly controlled via the Port 0 SFR. Port 0 is also the

multiplexed low order address and data bus during accesses to

external program or data memory.

Figure 57 shows a typical bit latch and I/O buffer for a Port 0

port pin. The bit latch (one bit in the port’s SFR) is represented

as a Type D flip-flop, which clocks in a value from the internal

bus in response to a write to latch signal from the CPU. The Q

output of the flip-flop is placed on the internal bus in response

to a read latch signal from the CPU. The level of the port pin

itself is placed on the internal bus in response to a read pin

signal from the CPU. Some instructions that read a port activate

the read latch signal, and others activate the read pin signal. See

the Read-Modify-Write Instructions section for details.

CONTROL

READ

LATCH

INTERNAL

BUS

WRITE

TO LATCH

READ

LATCH

ADDR/DATA

P0.x

03260-0-056

Figure 57. Port 0 Bit Latch and I/O Buffer

As shown in Figure 57, the output drivers of Port 0 pins are

switchable to an internal ADDR and ADDR/DATA bus by an

internal control signal for use in external memory accesses.

During external memory accesses, the P0 SFR has 1s written to

it, i.e., all of its bit latches become 1. When accessing external

memory, the control signal in Figure 57 goes high, enabling

push-pull operation of the output pin from the internal address

or data bus (ADDR/DATA line). Therefore, no external pull-ups

are required on Port 0 for it to access external memory.

In general-purpose I/O port mode, Port 0 pins that have 1s writ-

ten to them via the Port 0 SFR are configured as open-drain and

will therefore float. In this state, Port 0 pins can be used as high

impedance inputs. This is represented in Figure 57 by the NAND

gate whose output remains high as long as the control signal is

low, thereby disabling the top FET. External pull-up resistors are

therefore required when Port 0 pins are used as general-purpose

outputs. Port 0 pins with 0s written to them drive a logic low

output voltage (VOL) and are capable of sinking 1.6 mA.

Port 1

Port 1 is also an 8-bit port directly controlled via the P1 SFR.

Port 1 digital output capability is not supported on this device.

Port 1 pins can be configured as digital inputs or analog inputs.

By (power-on) default, these pins are configured as analog

inputs, i.e., 1 written in the corresponding Port 1 register bit. To

configure any of these pins as digital inputs, the user should

write a 0 to these port bits to configure the corresponding pin as

a high impedance digital input. These pins also have various

secondary functions as described in Table 25.

Table 25. Port 1 Alternate Pin Functions

Pin No. Alternate Function

P1.0 T2 (Timer/Counter 2 External Input)

P1.1 T2EX (Timer/Counter 2 Capture/Reload Trigger)

P1.5 SS (Slave Select for the SPI Interface)

READ

LATCH

INTERNAL

BUS

WRITE

TO LATCH

READ

LATCH P1.x

TO ADC

03260-0-057

Figure 58. Port 1 Bit Latch and I/O Buffer

Port 2

Port 2 is a bidirectional port with internal pull-up resistors

directly controlled via the P2 SFR. Port 2 also emits the high-

order address bytes during fetches from external program

memory, and middle and high order address bytes during

accesses to the 24-bit external data memory space.

As shown in Figure 59, the output drivers of Port 2 are switch-

able to an internal ADDR and ADDR/DATA bus by an internal

control signal for use in external memory accesses (as for

Port 0). In external memory addressing mode (CONTROL = 1),

the port pins feature push-pull operation controlled by the

internal address bus (ADDR line). However, unlike the P0 SFR

during external memory accesses, the P2 SFR remains unchanged.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 58 of 88

In general-purpose I/O port mode, Port 2 pins that have 1s

written to them are pulled high by the internal pull-ups

(Figure 60) and, in that state, can be used as inputs. As inputs,

Port 2 pins being pulled externally low source current because

of the internal pull-up resistors. Port 2 pins with 0s written to

them drive a logic low output voltage (VOL) and are capable of

sinking 1.6 mA.

P2.6 and P2.7 can also be used as PWM outputs. When they are

selected as the PWM outputs via the CFG841/CFG842 SFR, the

PWM outputs overwrite anything written to P2.6 or P2.7.

CONTROL

READ

LATCH

INTERNAL

BUS

WRITE

TO LATCH

READ

LATCH

ADDR

P2.x

INTERNAL

PULL-UP*

*SEE FOLLOWING FIGURE FOR

DETAILS OF INTERNAL PULL-UP

03260-0-058

Figure 59. Port 2 Bit Latch and I/O Buffer

FROM

PORT

LATCH

2 CLK

DELAY

DVDD

Px.x

03260-0-059

Figure 60. Internal Pull-Up Configuration

Port 3

Port 3 is a bidirectional port with internal pull-ups directly

controlled via the P3 SFR. Port 3 pins that have 1s written to

them are pulled high by the internal pull-ups and, in that state,

can be used as inputs. As inputs, Port 3 pins being pulled

externally low source current because of the internal pull-ups.

Port 3 pins with 0s written to them will drive a logic low output

voltage (VOL) and are capable of sinking 4 mA. Port 3 pins also

have various secondary functions as described in Table 26. The

alternate functions of Port 3 pins can be activated only if the

corresponding bit latch in the P3 SFR contains a 1. Otherwise,

the port pin is stuck at 0.

Table 26. Port 3 Alternate Pin Functions

Pin No. Alternate Function

P3.0 RxD (UART Input Pin) (or Serial Data I/O in Mode 0)

P3.1 TxD (UART Output Pin) (or Serial Clock Output in Mode 0)

P3.2 INT0 (External Interrupt 0)

P3.3 INT1 (External Interrupt 1)/PWM 1/MISO

P3.4 T0 (Timer/Counter 0 External Input)

PWM External Clock/PWM 0

P3.5 T1 (Timer/Counter 1 External Input)

P3.6 WR (External Data Memory Write Strobe)

P3.7 RD (External Data Memory Read Strobe)

P3.3 and P3.4 can also be used as PWM outputs. When they are

selected as the PWM outputs via the CFG841/CFG842 SFR, the

PWM outputs overwrite anything written to P3.4 or P3.3.

READ

LATCH

INTERNAL

BUS

WRITE

TO LATCH

READ

LATCH

P3.x

INTERNAL

PULL-UP*

*SEE PREVIOUS FIGURE

FOR DETAILS OF

INTERNAL PULL-UP

ALTERNATE

OUTPUT

FUNCTION

ALTERNATE

INPUT

FUNCTION

03260-0-060

Figure 61. Port 3 Bit Latch and I/O Buffer

Additional Digital I/O

In addition to the port pins, the dedicated SPI/I2C pins (SCLOCK

and SDATA/MOSI) also feature both input and output func-

tions. Their equivalent I/O architectures are illustrated in

Figure 62 and Figure 64, respectively, for SPI operation and in

Figure 63 and Figure 65 for I2C operation. Notice that in I2C

mode (SPE = 0), the strong pull-up FET (Q1) is disabled,

leaving only a weak pull-up (Q2) present. By contrast, in SPI

mode (SPE = 1) the strong pull-up FET (Q1) is controlled

directly by SPI hardware, giving the pin push-pull capability.

In I2C mode (SPE = 0), two pull-down FETs (Q3 and Q4)

operate in parallel to provide an extra 60% or 70% of current

sinking capability. In SPI mode (SPE = 1), however, only one of

the pull-down FETs (Q3) operates on each pin, resulting in sink

capabilities identical to that of Port 0 and Port 2 pins. On the

input path of SCLOCK, notice that a Schmitt trigger conditions

the signal going to the SPI hardware to prevent false triggers

(double triggers) on slow incoming edges. For incoming signals

from the SCLOCK and SDATA pins going to I2C hardware, a

filter conditions the signals to reject glitches of up to 50 ns in

duration.

Notice also that direct access to the SCLOCK and SDATA/

MOSI pins is afforded through the SFR interface in I2C master

mode. Therefore, if you are not using the SPI or I2C functions,

you can use these two pins to give additional high current

digital outputs.

SCHMITT

TRIGGER

Q1 Q2 (OFF)

DVDD

Q4 (OFF)

SCLOCK

SPE = 1 (SPI ENABLE)

HARDWARE SPI

(MASTER/SLAVE)

03260-0-061

Figure 62. SCLOCK Pin I/O Functional Equivalent in SPI Mode

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 59 of 88

MOSI is shared with P3.3 and, as such, has the same

configuration as the one shown in Figure 61.

MCO

I2CM Q3

SCLOCK

(OFF)

50ns GLITCH

REJECTION FILTER

SPE = 0 (I

C ENABLE)

HARDWARE I

(SLAVE ONLY)

SFR

BITS

03260-0-062

Figure 63. SCLOCK Pin I/O Functional Equivalent in I2C Mode

Q1 Q2 (OFF)

Q4 (OFF)

SDATA/

MOSI

SPE = 1 (SPI ENABLE)

HARDWARE SPI

(MASTER/SLAVE)

03260-0-097

Figure 64. SDATA/MOSI Pin I/O Functional Equivalent in SPI Mode

MCO

SDATA/

MOSI

(OFF)

50ns GLITCH

REJECTION FILTER

SPE = 0 (I

C ENABLE)

HARDWARE I

(SLAVE ONLY)

SFR

BITS

MCI

MDE

I2CM

03260-0-063

Figure 65. SDATA/MOSI Pin I/O Functional Equivalent in I2C Mode

Read-Modify-Write Instructions

Some 8051 instructions that read a port read the latch while

others read the pin. The instructions that read the latch rather

than the pins are the ones that read a value, possibly change it,

and then rewrite it to the latch. These are called read-modify-

write instructions, which are listed below. When the destination

operand is a port or a port bit, these instructions read the latch

rather than the pin.

Table 27. Read-Write-Modify Instructions

Instruction Description

ANL Logical AND, e.g., ANL P1, A

ORL (Logical OR, e.g., ORL P2, A

XRL (Logical EX-OR, e.g., XRL P3, A

JBC Jump if Bit = 1 and clear bit, e.g., JBC P1.1,

LABEL

CPL Complement bit, e.g., CPL P3.0

INC Increment, e.g., INC P2

DEC Decrement, e.g., DEC P2

DJNZ Decrement and Jump if Not Zero, e.g., DJNZ

P3, LABEL

MOV PX.Y, C1 Move Carry to Bit Y of Port X

CLR PX.Y1 Clear Bit Y of Port X

SETB PX.Y1 Set Bit Y of Port X

1 These instructions read the port byte (all 8 bits), modify the addressed bit,

and then write the new byte back to the latch.

Read-modify-write instructions are directed to the latch rather

than to the pin to avoid a possible misinterpretation of the

voltage level of a pin. For example, a port pin might be used to

drive the base of a transistor. When 1 is written to the bit, the

transistor is turned on. If the CPU then reads the same port bit

at the pin rather than the latch, it reads the base voltage of the

transistor and interprets it as a Logic 0. Reading the latch rather

than the pin returns the correct value of 1.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 60 of 88

Timers/Counters

The ADuC841/ADuC842/ADuC843 have three 16-bit timer/

counters: Timer 0, Timer 1, and Timer 2. The timer/counter

hardware is included on-chip to relieve the processor core of the

overhead inherent in implementing timer/counter functionality

in software. Each timer/counter consists of two 8-bit registers:

THx and TLx (x = 0, 1, and 2). All three can be configured to

operate either as timers or as event counters.

In timer function, the TLx register is incremented every

machine cycle. Thus, one can think of it as counting machine

cycles. Since a machine cycle on a single-cycle core consists of

one core clock period, the maximum count rate is the core clock

frequency.

In counter function, the TLx register is incremented by a 1-to-0

transition at its corresponding external input pin: T0, T1, or T2.

When the samples show a high in one cycle and a low in the

next cycle, the count is incremented. Since it takes two machine

cycles (two core clock periods) to recognize a 1-to-0 transition,

the maximum count rate is half the core clock frequency.

There are no restrictions on the duty cycle of the external input

signal, but to ensure that a given level is sampled at least once

before it changes, it must be held for a minimum of one full

machine cycle. User configuration and control of all timer

operating modes is achieved via three SFRs:

TMOD, TCON Control and configuration for

Timers 0 and 1.

T2CON Control and configuration for

Timer 2.

TMOD Timer/Counter 0 and 1 Mode

SFR Address 89H

Power-On Default 00H

Bit Addressable No

Table 28. TMOD SFR Bit Designations

Bit No. Name Description

7 Gate Timer 1 Gating Control.

Set by software to enable Timer/Counter 1 only while the INT1 pin is high and the TR1 control bit is set.

Cleared by software to enable Timer 1 whenever the TR1 control bit is set.

6 C/T Timer 1 Timer or Counter Select Bit.

Set by software to select counter operation (input from T1 pin).

Cleared by software to select timer operation (input from internal system clock).

5 M1 Timer 1 Mode Select Bit 1 (Used with M0 Bit).

Timer 1 Mode Select Bit 0.

M1 M0

0 0 TH1 operates as an 8-bit timer/counter. TL1 serves as 5-bit prescaler.

0 1 16-Bit Timer/Counter. TH1 and TL1 are cascaded; there is no prescaler.

1 0 8-Bit Autoreload Timer/Counter. TH1 holds a value that is to be reloaded into TL1 each time it

overflows.

1 1 Timer/Counter 1 Stopped.

3 Gate Timer 0 Gating Control.

Set by software to enable Timer/Counter 0 only while the INT0 pin is high and the TR0 control bit is set.

Cleared by software to enable Timer 0 whenever the TR0 control bit is set.

2 C/T Timer 0 Timer or Counter Select Bit.

Set by software to select counter operation (input from T0 pin).

Cleared by software to select timer operation (input from internal system clock).

1 M1 Timer 0 Mode Select Bit 1.

Timer 0 Mode Select Bit 0.

M1 M0

0 0 TH0 operates as an 8-bit timer/counter. TL0 serves as a 5-bit prescaler.

0 1 16-Bit Timer/Counter. TH0 and TL0 are cascaded; there is no prescaler.

1 0 8-Bit Autoreload Timer/Counter. TH0 holds a value that is to be reloaded into TL0 each time it

overflows.

0 M0

1 1 TL0 is an 8-bit timer/counter controlled by the standard Timer 0 control bits.

TH0 is an 8-bit timer only, controlled by Timer 1 control bits.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 61 of 88

TCON

Timer/Counter 0 and 1

Control Register

SFR Address 88H

Power-On Default 00H

Bit Addressable Yes

Table 29. TCON SFR Bit Designations

Bit No. Name Description

7 TF1 Timer 1 Overflow Flag.

Set by hardware on a Timer/Counter 1 overflow.

Cleared by hardware when the program counter (PC) vectors to the interrupt service routine.

6 TR1 Timer 1 Run Control Bit.

Set by the user to turn on Timer/Counter 1.

Cleared by the user to turn off Timer/Counter 1.

5 TF0 Timer 0 Overflow Flag.

Set by hardware on a Timer/Counter 0 overflow.

Cleared by hardware when the PC vectors to the interrupt service routine.

4 TR0 Timer 0 Run Control Bit.

Set by the user to turn on Timer/Counter 0.

Cleared by the user to turn off Timer/Counter 0.

3 IE11 External Interrupt 1 (INT1) Flag.

Set by hardware by a falling edge or by a zero level being applied to the external interrupt pin, INT1, depending on

the state of Bit IT1.

Cleared by hardware when the PC vectors to the interrupt service routine only if the interrupt was transition-

activated. If level-activated, the external requesting source controls the request flag, rather than the on-chip

hardware.

2 IT11 External Interrupt 1 (IE1) Trigger Type.

Set by software to specify edge-sensitive detection, i.e., 1-to-0 transition.

Cleared by software to specify level-sensitive detection, i.e., zero level.

1 IE01 External Interrupt 0 (INT0) Flag.

Set by hardware by a falling edge or by a zero level being applied to external interrupt pin INT0, depending on the

state of Bit IT0.

Cleared by hardware when the PC vectors to the interrupt service routine only if the interrupt was transition-

activated. If level-activated, the external requesting source controls the request flag, rather than the on-chip

hardware.

0 IT01 External Interrupt 0 (IE0) Trigger Type.

Set by software to specify edge-sensitive detection, i.e.,1-to-0 transition.

Cleared by software to specify level-sensitive detection, i.e., zero level.

1These bits are not used in the control of Timer/Counter 0 and 1, but are used instead in the control and monitoring of the external INT0 and INT1 interrupt pins.

Timer/Counter 0 and 1 Data Registers

Each timer consists of two 8-bit registers. These can be used as

independent registers or combined into a single 16-bit register

depending on the timer mode configuration.

TH0 and TL0

Timer 0 high byte and low byte.

SFR Address = 8CH 8AH, respectively.

TH1 and TL1

Timer 1 high byte and low byte.

SFR Address = 8DH, 8BH, respectively.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 62 of 88

TIMER/COUNTER 0 AND 1 OPERATING MODES

The following sections describe the operating modes for

Timer/Counters 0 and 1. Unless otherwise noted, assume that

these modes of operation are the same for both Timer 0 and

Timer 1.

Mode 0 (13-Bit Timer/Counter)

Mode 0 configures an 8-bit timer/counter. Figure 66 shows

Mode 0 operation. Note that the divide-by-12 prescaler is not

present on the single-cycle core.

CORE

CLK

P3.4/T0

P3.2/INT0

TR0

TF0

TH0

(8 BITS)

INTERRUPT

Tl0

(5 BITS)

CONTROL

GATE

C/T = 1

C/T = 0

03260-0-064

Figure 66. Timer/Counter 0, Mode 0

In this mode, the timer register is configured as a 13-bit register.

As the count rolls over from all 1s to all 0s, it sets the timer

overflow flag, TF0. TF0 can then be used to request an interrupt.

The counted input is enabled to the timer when TR0 = 1 and

either Gate = 0 or INT0 = 1. Setting Gate = 1 allows the timer to

be controlled by external input INT0 to facilitate pulse-width

measurements. TR0 is a control bit in the special function

all 8 bits of TH0 and the lower five bits of TL0. The upper 3 bits

of TL0 are indeterminate and should be ignored. Setting the run

flag (TR0) does not clear the registers.

Mode 1 (16-Bit Timer/Counter)

Mode 1 is the same as Mode 0, except that the Mode 1 timer

Figure 67.

CORE

CLK

CONTROL

P3.4/T0

GATE

TR0

TF0

TL0

(8 BITS) TH0

(8 BITS)

INTERRUPT

P3.2/INT0

C/T = 0

C/T = 1

03260-0-066

Figure 67. Timer/Counter 0, Mode 1

Mode 2 (8-Bit Timer/Counter with Autoreload)

Mode 2 configures the timer register as an 8-bit counter (TL0)

with automatic reload, as shown in Figure 68. Overflow from TL0

not only sets TF0, but also reloads TL0 with the contents of TH0,

which is preset by software. The reload leaves TH0 unchanged.

CONTROL

TF0

TL0

(8 BITS)

INTERRUPT

RELOAD

TH0

(8 BITS)

CORE

CLK

P3.4/T0

GATE

TR0

P3.2/INT0

C/T = 0

C/T = 1

03260-0-067

Figure 68. Timer/Counter 0, Mode 2

Mode 3 (Two 8-Bit Timer/Counters)

Mode 3 has different effects on Timer 0 and Timer 1. Timer 1 in

Mode 3 simply holds its count. The effect is the same as setting

TR1 = 0. Timer 0 in Mode 3 establishes TL0 and TH0 as two

separate counters. This configuration is shown in Figure 69. TL0

uses the Timer 0 control bits: C/T, Gate, TR0, INT0, and TF0.

TH0 is locked into a timer function (counting machine cycles)

and takes over the use of TR1 and TF1 from Timer 1. Thus,

TH0 now controls the Timer 1 interrupt. Mode 3 is provided for

applications requiring an extra 8-bit timer or counter.

When Timer 0 is in Mode 3, Timer 1 can be turned on and off

by switching it out of and into its own Mode 3, or it can still be

used by the serial interface as a baud rate generator. In fact, it

can be used in any application not requiring an interrupt from

Timer 1 itself.

CONTROL

TF0

TL0

(8 BITS)

INTERRUPT

CORE

CLK

P3.4/T0

GATE

TR0

TF1

TH0

(8 BITS)

INTERRUPT

CORE

CLK/12

TR1

P3.2/INT0

C/T = 0

C/T = 1

03260-0-068

Figure 69. Timer/Counter 0, Mode 3

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 63 of 88

Table 30. T2CON SFR Bit Designations

Bit No. Name Description

7 TF2 Timer 2 Overflow Flag.

Set by hardware on a Timer 2 overflow. TF2 cannot be set when either RCLK = 1 or TCLK = 1.

Cleared by user software.

6 EXF2 Timer 2 External Flag.

Set by hardware when either a capture or reload is caused by a negative transition on T2EX and EXEN2 = 1.

Cleared by user software.

5 RCLK Receive Clock Enable Bit.

Set by the user to enable the serial port to use Timer 2 overflow pulses for its receive clock in serial port Modes 1 and 3.

Cleared by the user to enable Timer 1 overflow to be used for the receive clock.

4 TCLK Transmit Clock Enable Bit.

Set by the user to enable the serial port to use Timer 2 overflow pulses for its transmit clock in serial port Modes 1 and 3.

Cleared by the user to enable Timer 1 overflow to be used for the transmit clock.

3 EXEN2 Timer 2 External Enable Flag.

Set by the user to enable a capture or reload to occur as a result of a negative transition on T2EX if Timer 2 is not being

used to clock the serial port.

Cleared by the user for Timer 2 to ignore events at T2EX.

2 TR2 Timer 2 Start/Stop Control Bit.

Set by the user to start Timer 2.

Cleared by the user to stop Timer 2.

1 CNT2 Timer 2 Timer or Counter Function Select Bit.

Set by the user to select counter function (input from external T2 pin).

Cleared by the user to select timer function (input from on-chip core clock).

0 CAP2 Timer 2 Capture/Reload Select Bit.

Set by the user to enable captures on negative transitions at T2EX if EXEN2 = 1.

Cleared by the user to enable autoreloads with Timer 2 overflows or negative transitions at T2EX when EXEN2 = 1.

When either RCLK = 1 or TCLK = 1, this bit is ignored and the timer is forced to autoreload on Timer 2 overflow.

Timer/Counter 2 Data Registers

Timer/Counter 2 also has two pairs of 8-bit data registers

associated with it. These are used as both timer data registers

and as timer capture/reload registers.

TH2 and TL2

Timer 2, data high byte and low byte.

SFR Address = CDH, CCH, respectively.

RCAP2H and RCAP2L

Timer 2, capture/reload byte and low byte.

SFR Address = CBH, CAH, respectively.

T2CON Timer/Counter 2 Control Register

SFR Address C8H

Power-On Default 00H

Bit Addressable Yes

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 64 of 88

TIMER/COUNTER OPERATING MODES

The following sections describe the operating modes for

Timer/Counter 2. The operating modes are selected by bits in

the T2CON SFR, as shown in Table 31.

Table 31. T2CON Operating Modes

RCLK (or) TCLK CAP2 TR2 Mode

0 0 1 16-Bit Autoreload

0 1 1 16-Bit Capture

1 X 1 Baud Rate

X X 0 OFF

16-Bit Autoreload Mode

Autoreload mode has two options that are selected by Bit EXEN2

in T2CON. If EXEN2 = 0, then when Timer 2 rolls over, it not

only sets TF2 but also causes the Timer 2 registers to be

reloaded with the 16-bit value in registers RCAP2L and RCAP2H,

which are preset by software. If EXEN2 = 1, then Timer 2 still

performs the above, but with the added feature that a 1-to-0

transition at external input T2EX will also trigger the 16-bit

reload and set EXF2. Autoreload mode is illustrated in Figure 70.

16-Bit Capture Mode

Capture mode also has two options that are selected by bit

EXEN2 in T2CON. If EXEN2 = 0, then Timer 2 is a 16-bit timer

or counter that, upon overflowing, sets Bit TF2, the Timer 2

overflow bit, which can be used to generate an interrupt. If

EXEN2 = 1, then Timer 2 still performs the above, but a l-to-0

transition on external input T2EX causes the current value in

the Timer 2 registers, TL2 and TH2, to be captured into

registers RCAP2L and RCAP2H, respectively. In addition, the

transition at T2EX causes Bit EXF2 in T2CON to be set, and

EXF2, like TF2, can generate an interrupt. Capture mode is

illustrated in Figure 71. The baud rate generator mode is

selected by RCLK = 1 and/or TCLK = 1.

In either case, if Timer 2 is being used to generate the baud rate,

the TF2 interrupt flag will not occur. Therefore, Timer 2

interrupts will not occur, so they do not have to be disabled. In

this mode, the EXF2 flag, however, can still cause interrupts,

which can be used as a third external interrupt. Baud rate

generation is described as part of the UART serial port

operation in the following section.

CORE

CLK*

C/T2 = 0

C/T2 = 1

TR2

CONTROL

TL2

(8 BITS) TH2

(8 BITS)

RELOAD

TF2

EXF2

TIMER

INTERRUPT

EXEN2

CONTROL

TRANSITION

DETECTOR

T2EX

RCAP2L RCAP2H

*CORE CLK IS DEFINED BY THE CD BITS IN PLLCON

03260-0-069

Figure 70. Timer/Counter 2, 16-Bit Autoreload Mode

TF2

CORE

CLK

TR2

CONTROL

TL2

(8 BITS) TH2

(8 BITS)

CAPTURE

EXF2

TIMER

INTERRUPT

EXEN2

CONTROL

TRANSITION

DETECTOR

T2EX

RCAP2L RCAP2H

C/T2 = 0

C/T2 = 1

*CORE CLK IS DEFINED BY THE CD BITS IN PLLCON

03260-0-070

Figure 71. Timer/Counter 2, 16-Bit Capture Mode

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 65 of 88

UART SERIAL INTERFACE

The serial port is full-duplex, meaning it can transmit and

receive simultaneously. It is also receive-buffered, meaning it

can begin receiving a second byte before a previously received

byte has been read from the receive register. However, if the first

byte still has not been read by the time reception of the second

byte is complete, the first byte is lost. The physical interface to

the serial data network is via Pins RxD(P3.0) and TxD(P3.1),

while the SFR interface to the UART is comprised of SBUF and

SCON, as described below.

SBUF

Both the serial port receive and transmit registers are accessed

through the SBUF SFR (SFR address = 99H). Writing to SBUF

loads the transmit register, and reading SBUF accesses a

physically separate receive register.

SCON UART Serial Port Control Register

SFR Address 98H

Power-On Default 00H

Bit Addressable Yes

Table 32. SCON SFR Bit Designations

Bit No. Name Description

7 SM0 UART Serial Mode Select Bits.

These bits select the serial port operating mode as follows:

SM0 SM1 Selected Operating Mode.

0 0 Mode 0: Shift Register, fixed baud rate (Core_Clk/2).

0 1 Mode 1: 8-bit UART, variable baud rate.

1 0 Mode 2: 9-bit UART, fixed baud rate (Core_Clk/32) or (Core_Clk/16).

6 SM1

1 1 Mode 3: 9-bit UART, variable baud rate.

5 SM2 Multiprocessor Communication Enable Bit.

Enables multiprocessor communication in Modes 2 and 3.

In Mode 0, SM2 must be cleared.

In Mode 1, if SM2 is set, RI is not activated if a valid stop bit was not received. If SM2 is cleared, RI is set as soon as the

byte of data has been received.

In Modes 2 or 3, if SM2 is set, RI is not activated if the received 9th data bit in RB8 is 0.

If SM2 is cleared, RI is set as soon as the byte of data has been received.

4 REN Serial Port Receive Enable Bit.

Set by user software to enable serial port reception.

Cleared by user software to disable serial port reception.

3 TB8 Serial Port Transmit (Bit 9).

The data loaded into TB8 is the 9th data bit transmitted in Modes 2 and 3.

2 RB8 Serial Port Receiver Bit 9.

The 9th data bit received in Modes 2 and 3 is latched into RB8. For Mode 1, the stop bit is latched into RB8.

1 TI Serial Port Transmit Interrupt Flag.

Set by hardware at the end of the 8th bit in Mode 0, or at the beginning of the stop bit in Modes 1, 2, and 3.

TI must be cleared by user software.

0 RI Serial Port Receive Interrupt Flag.

Set by hardware at the end of the 8th bit in Mode 0, or halfway through the stop bit in Modes 1, 2, and 3.

RI must be cleared by software.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 66 of 88

Mode 0: 8-Bit Shift Register Mode

Mode 0 is selected by clearing both the SM0 and SM1 bits in the

SFR SCON. Serial data enters and exits through RxD. TxD out-

puts the shift clock. Eight data bits are transmitted or received.

Transmission is initiated by any instruction that writes to SBUF.

The data is shifted out of the RxD line. The 8 bits are transmitted

with the least significant bit (LSB) first.

Reception is initiated when the receive enable bit (REN) is 1

and the receive interrupt bit (RI) is 0. When RI is cleared, the

data is clocked into the RxD line, and the clock pulses are

output from the TxD line.

Mode 1: 8-Bit UART, Variable Baud Rate

Mode 1 is selected by clearing SM0 and setting SM1. Each data

byte (LSB first) is preceded by a start bit (0) and followed by a

stop bit (1). Therefore, 10 bits are transmitted on TxD or are

received on RxD. The baud rate is set by the Timer 1 or Timer 2

overflow rate, or a combination of the two (one for transmission

and the other for reception).

Transmission is initiated by writing to SBUF. The write to SBUF

signal also loads a 1 (stop bit) into the 9th bit position of the

transmit shift register. The data is output bit by bit until the stop

bit appears on TxD and the transmit interrupt flag (TI) is

automatically set, as shown in Figure 72.

TxD

(

SCON.1)

START

BIT

D0 D1 D2 D3 D4 D5 D6 D7

STOP BIT

SET INTERRUPT

I.E., READY FOR MORE DATA

03260-0-072

Figure 72. UART Serial Port Transmission, Mode 1

Reception is initiated when a 1-to-0 transition is detected on

RxD. Assuming a valid start bit is detected, character reception

continues. The start bit is skipped and the 8 data bits are

clocked into the serial port shift register. When all 8 bits have

been clocked in, the following events occur:

• The 8 bits in the receive shift register are latched into SBUF.

• The 9th bit (stop bit) is clocked into RB8 in SCON.

• The receiver interrupt flag (RI) is set.

This is the case if, and only if, all of the following conditions are

met at the time the final shift pulse is generated:

• RI = 0

• Either SM2 = 0 or SM2 = 1

• The received stop bit = 1

If any of these conditions is not met, the received frame is

irretrievably lost, and RI is not set.

Mode 2: 9-Bit UART with Fixed Baud Rate

Mode 2 is selected by setting SM0 and clearing SM1. In this

mode, the UART operates in 9-bit mode with a fixed baud rate.

The baud rate is fixed at Core_Clk/32 by default, although by

setting the SMOD bit in PCON, the frequency can be doubled

to Core_Clk/16. Eleven bits are transmitted or received: a start

bit (0), 8 data bits, a programmable 9th bit, and a stop bit (1).

The 9th bit is most often used as a parity bit, although it can be

used for anything, including a 9th data bit if required.

To transmit, the 8 data bits must be written into SBUF. The 9th

bit must be written to TB8 in SCON. When transmission is

initiated, the 8 data bits (from SBUF) are loaded onto the

transmit shift register (LSB first). The contents of TB8 are loaded

into the 9th bit position of the transmit shift register. The

transmission starts at the next valid baud rate clock. The TI flag

is set as soon as the stop bit appears on TxD.

Reception for Mode 2 is similar to that of Mode 1. The 8 data

bytes are input at RxD (LSB first) and loaded onto the receive

shift register. When all 8 bits have been clocked in, the following

events occur:

• The 8 bits in the receive shift register are latched into SBUF.

• The 9th data bit is latched into RB8 in SCON.

• The receiver interrupt flag (RI) is set.

This is the case if, and only if, all of the following conditions are

met at the time the final shift pulse is generated:

• RI = 0

• Either SM2 = 0 or SM2 = 1

• The received stop bit = 1

If any of these conditions is not met, the received frame is

irretrievably lost, and RI is not set.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 67 of 88

Mode 3: 9-Bit UART with Variable Baud Rate

Mode 3 is selected by setting both SM0 and SM1. In this mode,

the 8051 UART serial port operates in 9-bit mode with a vari-

able baud rate determined by either Timer 1 or Timer 2. The

operation of the 9-bit UART is the same as for Mode 2, but the

baud rate can be varied as for Mode 1.

In all four modes, transmission is initiated by any instruction

that uses SBUF as a destination register. Reception is initiated in

Mode 0 by the condition RI = 0 and REN = 1. Reception is

initiated in the other modes by the incoming start bit if REN = 1.

UART Serial Port Baud Rate Generation

Mode 0 Baud Rate Generation

The baud rate in Mode 0 is fixed.

Mode 0 Baud Rate = (Core Clock Frequency/12)

Mode 2 Baud Rate Generation

The baud rate in Mode 2 depends on the value of the SMOD bit

in the PCON SFR. If SMOD = 0, the baud rate is 1/32 of the

core clock. If SMOD = 1, the baud rate is 1/16 of the core clock:

Mode 2 Baud Rate = (2SMOD/32 × [Core Clock Frequency])

Modes 1 and 3 Baud Rate Generation

The baud rates in Modes 1 and 3 are determined by the over-

flow rate in Timer 1 or Timer 2, or in both (one for transmit

and the other for receive).

Timer 1 Generated Baud Rates

When Timer 1 is used as the baud rate generator, the baud rates

in Modes 1 and 3 are determined by the Timer 1 overflow rate

and the value of SMOD as follows:

Modes 1 and 3 Baud Rate = (2SMOD/32 × (Timer 1 Overflow Rate)

The Timer 1 interrupt should be disabled in this application.

The timer itself can be configured for either timer or counter

operation, and in any of its three running modes. In the most

typical application, it is configured for timer operation in the

autoreload mode (high nibble of TMOD = 0010 binary). In that

case, the baud rate is given by the formula

Modes 1 and 3 Baud Rate =

(2SMOD/32) × (Core Clock/ [256 − TH1])

Timer 2 Generated Baud Rates

Baud rates can also be generated using Timer 2. Using Timer 2

is similar to using Timer 1 in that the timer must overflow 16

times before a bit is transmitted/received. Because Timer 2 has a

16-bit autoreload mode, a wider range of baud rates is possible

using Timer 2.

Modes 1 and 2 Baud Rate = (1/16) × (Timer 2 Overflow Rate)

Therefore, when Timer 2 is used to generate baud rates, the

timer increments every two clock cycles rather than every core

machine cycle as before. Thus, it increments six times faster

than Timer 1, and therefore baud rates six times faster are possi-

ble. Because Timer 2 has 16-bit autoreload capability, very low

baud rates are still possible.

Timer 2 is selected as the baud rate generator by setting the

TCLK and/or RCLK in T2CON. The baud rates for transmit

and receive can be simultaneously different. Setting RCLK and/

or TCLK puts Timer 2 into its baud rate generator mode as

shown in Figure 73.

In this case, the baud rate is given by the formula

Modes 1 and 3 Baud Rate =

(Core Clock)/(16 × [65536 − (RCAP 2H, RCAP 2L)])

CORE

CLK*

TR2

CONTROL

TL2

(8 BITS) TH2

(8 BITS)

RELOAD

EXEN2

CONTROL

T2EX

TRANSITION

DETECTOR

EXF 2 TIMER 2

INTERRUPT

NOTE: AVAILABILITY OF ADDITIONA

EXTERNAL INTERRUP

RCAP2L RCAP2H

TIMER 2

OVERFLOW

RCLK

TCLK

CLOCK

10 SMOD

TIMER 1

OVERFLOW

C/T2 = 0

C/T2 = 1

*CORE CLK IS DEFINED BY THE CD BITS IN PLLCON

03260-0-073

Figure 73. Timer 2, UART Baud Rates

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 68 of 88

Timer 3 Generated Baud Rates

The high integer dividers in a UART block mean that high

speed baud rates are not always possible using some particular

crystals. For example, using a 12 MHz crystal, a baud rate of

115200 is not possible. To address this problem, the part has

added a dedicated baud rate timer (Timer 3) specifically for

generating highly accurate baud rates. Timer 3 can be used

instead of Timer 1 or Timer 2 for generating very accurate high

speed UART baud rates including 115200 and 230400. Timer 3

also allows a much wider range of baud rates to be obtained. In

fact, every desired bit rate from 12 bit/s to 393216 bit/s can be

generated to within an error of ±0.8%. Timer 3 also frees up the

other three timers, allowing them to be used for different

applications. A block diagram of Timer 3 is shown in Figure 74.

(1 + T3FD/64)

T3 RX/TX

CLOCK

CORE

CLK

T3EN

RX CLOCK

TX CLOCK

TIMER 1/TIMER 2

RX CLOCK

FRACTIONA

DIVIDER

TIMER 1/TIMER 2

TX CLOCK

DIV

03260-0-074

Figure 74. Timer 3, UART Baud Rates

Two SFRs (T3CON and T3FD) are used to control Timer 3.

T3CON is the baud rate control SFR, allowing Timer 3 to be

used to set up the UART baud rate, and setting up the binary

divider (DIV).

The appropriate value to write to the DIV2-1-0 bits can be

calculated using the following formula where fCORE is defined in

PLLCON SFR. Note that the DIV value must be rounded down.

()

2log

log ⎟

⎟

⎠

⎞

⎜

⎝

⎛

=RateBaud

DIV

CORE

T3FD is the fractional divider ratio required to achieve the

required baud rate. The appropriate value for T3FD can be

calculated with the following formula:

31−

=−RateBaud

FDT DIV CORE

Note that T3FD should be rounded to the nearest integer. Once

the values for DIV and T3FD are calculated, the actual baud rate

can be calculated with the following formula:

()

6432

1+×

=−FDTf

RateBaudActual DIV CORE

For example, to get a baud rate of 115200 while operating at

16.7 MHz, i.e., CD = 0

(

)

(

)

()

HFDT

DIV

099641152002/1677721623

318.32log/11520016/16777216log

2==−××=

Therefore, the actual baud rate is 114912 bit/s.

Table 33. T3CON SFR Bit Designations

Bit No. Name Description

7 T3BAUDEN T3UARTBAUD Enable.

Set to enable Timer 3 to generate the baud rate. When set, PCON.7, T2CON.4, and T2CON.5 are ignored.

Cleared to let the baud rate be generated as per a standard 8052.

6 Reserved.

5 Reserved.

4 Reserved.

3 Reserved.

2 DIV2 Binary Divider Factor.

1 DIV1 DIV2 DIV1 DIV0 Bin Divider

0 0 0 1

0 0 1 1

0 1 0 1

0 1 1 1

1 0 0 1

1 0 1 1

1 1 0 1

0 DIV0

1 1 1 1

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 69 of 88

Table 34. Commonly Used Baud Rates Using Timer 3 with the 16.777216 MHz PLL Clock

Ideal Baud CD DIV T3CON T3FD % Error

230400 0 2 82H 09H 0.25

115200 0 3 83H 09H 0.25

115200 1 2 82H 09H 0.25

115200 2 1 81H 09H 0.25

57600 0 4 84H 09H 0.25

57600 1 3 83H 09H 0.25

57600 2 2 82H 09H 0.25

57600 3 1 81H 09H 0.25

38400 0 4 84H 2DH 0.2

38400 1 3 83H 2DH 0.2

38400 2 2 82H 2DH 0.2

38400 3 1 81H 2DH 0.2

19200 0 5 85H 2DH 0.2

19200 1 4 84H 2DH 0.2

19200 2 3 83H 2DH 0.2

19200 3 2 82H 2DH 0.2

19200 4 1 81H 2DH 0.2

9600 0 6 86H 2DH 0.2

9600 1 5 85H 2DH 0.2

9600 2 4 84H 2DH 0.2

9600 3 3 83H 2DH 0.2

9600 4 2 82H 2DH 0.2

9600 5 1 81H 2DH 0.2

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 70 of 88

INTERRUPT SYSTEM

The ADuC841/ADuC842/ADuC843 provide a total of nine

interrupt sources with two priority levels. The control and

configuration of the interrupt system is carried out through

three interrupt-related SFRs:

IE Interrupt Enable Register

IP Interrupt Priority Register

IEIP2 Secondary Interrupt Enable Register

IE Interrupt Enable Register

SFR Address A8H

Power-On Default 00H

Bit Addressable Yes

Table 35. IE SFR Bit Designations

Bit No. Name Description

7 EA Set by the user to enable, or cleared to disable all interrupt sources.

6 EADC Set by the user to enable, or cleared to disable ADC interrupts.

5 ET2 Set by the user to enable, or cleared to disable Timer 2 interrupts.

4 ES Set by the user to enable, or cleared to disable UART serial port interrupts.

3 ET1 Set by the user to enable, or cleared to disable 0 Timer 1 interrupts.

2 EX1 Set by the user to enable, or cleared to disable External Interrupt 1.

1 ET0 Set by the user to enable, or cleared to disable Timer 0 interrupts.

0 EX0 Set by the user to enable, or cleared to disable External Interrupt 0 .

IP Interrupt Priority Register

SFR Address B8H

Power-On Default 00H

Bit Addressable Yes

Table 36. IP SFR Bit Designations

Bit No. Name Description

7 ---- Reserved.

6 PADC Written by the user to select the ADC interrupt priority (1 = High; 0 = Low).

5 PT2 Written by the user to select the Timer 2 interrupt priority (1 = High; 0 = Low).

4 PS Written by the user to select the UART serial port interrupt priority (1 = High; 0 = Low).

3 PT1 Written by the user to select the Timer 1 interrupt priority (1 = High; 0 = Low).

2 PX1 Written by the user to select External Interrupt 1 priority (1 = High; 0 = Low).

1 PT0 Written by the user to select the Timer 0 interrupt priority (1 = High; 0 = Low).

0 PX0 Written by the user to select External Interrupt 0 priority (1 = High; 0 = Low).

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 71 of 88

IEIP2 Secondary Interrupt Enable Register

SFR Address A9H

Power-On Default A0H

Bit Addressable No

Table 37. IEIP2 SFR Bit Designations

Bit No. Name Description

7 ---- Reserved.

6 PTI Priority for time interval interrupt.

5 PPSM Priority for power supply monitor interrupt.

4 PSI Priority for SPI/I2C interrupt.

3 ---- This bit must contain zero.

2 ETI Set by the user to enable, or cleared to disable time interval counter interrupts.

1 EPSMI Set by the user to enable, or cleared to disable power supply monitor interrupts.

0 ESI Set by the user to enable, or cleared to disable SPI or I2C serial port interrupts.

Interrupt Priority

The interrupt enable registers are written by the user to enable

individual interrupt sources, while the interrupt priority regis-

ters allow the user to select one of two priority levels for each

interrupt. An interrupt of a high priority may interrupt the

service routine of a low priority interrupt, and if two interrupts

of different priority occur at the same time, the higher level

interrupt is serviced first. An interrupt cannot be interrupted by

another interrupt of the same priority level. If two interrupts of

the same priority level occur simultaneously, a polling sequence

is observed as shown in Table 38.

Table 38. Priority within an Interrupt Level

Source Priority Description

PSMI 1 (Highest) Power Supply Monitor Interrupt.

WDS 2 Watchdog Timer Interrupt.

IE0 2 External Interrupt 0.

ADCI 3 ADC Interrupt.

TF0 4 Timer/Counter 0 Interrupt.

IE1 5 External Interrupt 1.

TF1 6 Timer/Counter 1 Interrupt.

ISPI/I2CI 7 SPI Interrupt/I2C Interrupt.

RI + TI 8 Serial Interrupt.

TF2 + EXF2 9 Timer/Counter 2 Interrupt.

TII 11(Lowest) Time Interval Counter Interrupt.

Interrupt Vectors

When an interrupt occurs, the program counter is pushed onto

the stack, and the corresponding interrupt vector address is

loaded into the program counter. The interrupt vector addresses

are shown in Table 39.

Table 39. Interrupt Vector Addresses

Source Vector Address

IE0 0003H

TF0 000BH

IE1 0013H

TF1 001BH

RI + TI 0023H

TF2 + EXF2 002BH

ADCI 0033H

ISPI/I2CI 003BH

PSMI 0043H

TII 0053H

WDS 005BH

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 72 of 88

HARDWARE DESIGN CONSIDERATIONS

This section outlines some of the key hardware design

considerations that must be addressed when integrating the

ADuC841/ADuC842/ADuC843 into any hardware system.

Clock Oscillator

The clock source for the parts can be generated by the internal

PLL or by an external clock input. To use the internal PLL, con-

nect a 32.768 kHz parallel resonant crystal between XTAL1 and

XTAL2, and connect a capacitor from each pin to ground as

shown in Figure 75. The parts contain an internal capacitance of

18 pF on the XTAL1 and XTAL2 pins, which is sufficient for

most watch crystals. This crystal allows the PLL to lock correctly

to give an fVCO of 16.777216 MHz. If no crystal is present, the

PLL will free run, giving an fVCO of 16.7 MHz ±20%. In this mode,

the CD bits are limited to CD = 1, giving a max core clock of

8.38 MHz. This is useful if an external clock input is required.

The part powers up and the PLL will free run; the user then

writes to the CFG842 SFR in software to enable the external clock

input on P3.4. Note that double the required clock must be pro-

vided externally since the part runs at CD = 1. A better solution is

to use the ADuC841 with the external clock.

For the ADuC841, connect the crystal in the same manner; external

capacitors should be connected as per the crystal manufacturer’s

recommendations. A minimum capacitance of 20 pF is

recommended on XTAL1 and XTAL2. The ADuC841 will not

operate if no crystal is present.

An external clock may be connected as shown in Figure 76 and

Figure 77.

XTAL2

XTAL1

TO INTERNAL

TIMING CIRCUITS

ADuC841/ADuC842/ADuC843

03260-0-076

Figure 75. External Parallel Resonant Crystal Connections

XTAL2

XTAL1

TO INTERNAL

TIMING CIRCUITS

ADuC841

03260-0-075

EXTERNAL

CLOCK

SOURCE

Figure 76. Connecting an External Clock Source (ADuC841)

P3.4 TO INTERNAL

TIMING CIRCUITS

ADuC842/ADuC843

03260-0-077

EXTERNAL

CLOCK

SOURCE

Figure 77. Connecting an External Clock Source (ADuC842/ADuC843)

Whether using the internal PLL or an external clock source, the

parts’ specified operational clock speed range is 400 kHz to

16.777216 MHz, (20 MHz, ADuC841). The core itself is static,

and functions all the way down to dc. But at clock speeds slower

that 400 kHz, the ADC can no longer function correctly. There-

fore, to ensure specified operation, use a clock frequency of at

least 400 kHz and no more than 20 MHz.

External Memory Interface

In addition to its internal program and data memories, the parts

can access up to 16 MBytes of external data memory (SRAM).

Note that the parts cannot access external program memory.

Figure 78 shows a hardware configuration for accessing up to

64 kBytes of external RAM. This interface is standard to any

8051 compatible MCU.

LATCH

SRAM

A8–A15

A0–A7

D0–D7

(DATA)

ADuC841/

ADuC842/

ADuC843

ALE

03260-0-078

Figure 78. External Data Memory Interface (64 kBytes Address Space)

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 73 of 88

If access to more than 64 kBytes of RAM is desired, a feature

unique to the ADuC841/ADuC842/ADuC843 allows address-

ing up to 16 MBytes of external RAM simply by adding an

additional latch as illustrated in Figure 79.

LATCH

ALE

LATCH

SRAM

A8–A15

A0–A7

D0–D7

(DATA)

A16–A23

ADuC841/

ADuC842/

ADuC843

03260-0-079

Figure 79. External Data Memory Interface (16 MBytes Address Space)

In either implementation, Port 0 (P0) serves as a multiplexed

address/data bus. It emits the low byte of the data pointer (DPL)

as an address, which is latched by a pulse of ALE prior to data

being placed on the bus by the ADuC841/ADuC842/ADuC843

(write operation) or by the SRAM (read operation). Port 2 (P2)

provides the data pointer page byte (DPP) to be latched by ALE,

followed by the data pointer high byte (DPH). If no latch is

connected to P2, DPP is ignored by the SRAM, and the 8051

standard of 64 kBytes external data memory access is maintained.

Power Supplies

The operational power supply voltage of the parts depends on

whether the part is the 3 V version or the 5 V version. The

specifications are given for power supplies within 2.7 V to 3.6 V

or ±5% of the nominal 5 V level.

Note that Figure 80 and Figure 81 refer to the PQFP package.

For the CSP package, connect the extra DVDD, DGND, AVDD,

and AGND in the same manner. Also, the paddle on the bottom

of the package should be soldered to a metal plate to provide

mechanical stability. This metal plate should not be connected

to ground.

Separate analog and digital power supply pins (AVDD and DVDD,

respectively) allow AVDD to be kept relatively free of the noisy

digital signals that are often present on the system DVDD line.

However, though you can power AVDD and DVDD from two

separate supplies if desired, you must ensure that they remain

within ±0.3 V of one another at all times to avoid damaging the

chip (as per the Absolute Maximum Ratings section). Therefore,

it is recommended that unless AVDD and DVDD are connected

directly together, back-to-back Schottky diodes should be con-

nected between them, as shown in Figure 80.

AGND

–

0.1µF

10µF

ANALOG SUPPLY

10µF

DGND

0.1µF

DIGITAL SUPPL

–

ADuC841/

ADuC842/

ADuC843

03260-0-080

Figure 80. External Dual-Supply Connections

As an alternative to providing two separate power supplies, the

user can help keep AVDD quiet by placing a small series resistor

and/or ferrite bead between it and DVDD, and then decoupling

AVDD separately to ground. An example of this configuration is

shown in Figure 81. With this configuration, other analog

circuitry (such as op amps and voltage reference) can be powered

from the AVDD supply line as well. The user will still want to

include back-to-back Schottky diodes between AVDD and DVDD

to protect them from power-up and power-down transient

conditions that could momentarily separate the two supply voltages.

AGND

DGND

DIGITAL SUPPL

–

+BEAD 1.6Ω

0.1µF

10µF

ADuC841/

ADuC842/

ADuC843

03260-0-081

Figure 81. External Single-Supply Connections

Notice that in both Figure 80 and Figure 81, a large value

(10 µF) reservoir capacitor sits on DVDD and a separate 10 µF

capacitor sits on AVDD. Also, local small-value (0.1 µF) capaci-

tors are located at each VDD pin of the chip. As per standard

design practice, be sure to include all of these capacitors, and

ensure the smaller capacitors are close to each AVDD pin with

trace lengths as short as possible. Connect the ground terminal

of each of these capacitors directly to the underlying ground

plane. Finally, note that at all times, the analog and digital ground

pins on the part must be referenced to the same system ground

reference point.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 74 of 88

Power Consumption

The currents consumed by the various sections of the part are

shown in Table 40. The core values given represent the current

drawn by DVDD, while the rest (ADC, DAC, voltage ref) are

pulled by the AVDD pin and can be disabled in software when

not in use. The other on-chip peripherals (such as the watchdog

timer and the power supply monitor) consume negligible

current, and are therefore lumped in with the core operating

current here. Of course, the user must add any currents sourced

by the parallel and serial I/O pins, and sourced by the DAC, in

order to determine the total current needed at the supply pins.

Also, current drawn from the DVDD supply increases by approxi-

mately 10 mA during Flash/EE erase and program cycles.

Table 40. Typical IDD of Core and Peripherals

VDD = 5 V VDD = 3 V

Core (Normal Mode) (2.2 nA × MCLK) (1.4 nA × MCLK)

ADC 1.7 mA 1.7 mA

DAC (Each) 250 µA 200 µA

Voltage Ref 200 µA 150 µA

Since operating DVDD current is primarily a function of clock

speed, the expressions for core supply current in Table 40 are

given as functions of MCLK, the core clock frequency. Plug in a

value for MCLK in hertz to determine the current consumed by

the core at that oscillator frequency. Since the ADC and DACs

can be enabled or disabled in software, add only the currents

from the peripherals you expect to use. And again, do not forget

to include current sourced by I/O pins, serial port pins, DAC

outputs, and so forth, plus the additional current drawn during

Flash/EE erase and program cycles. A software switch allows the

chip to be switched from normal mode into idle mode, and also

into full power-down mode. Brief descriptions of idle and

power-down modes follow.

Power Saving Modes

In idle mode, the oscillator continues to run, but the core clock

generated from the PLL is halted. The on-chip peripherals

continue to receive the clock, and remain functional. The CPU

status is preserved with the stack pointer and program counter,

and all other internal registers maintain their data during idle

mode. Port pins and DAC output pins retain their states in this

mode. The chip recovers from idle mode upon receiving any

enabled interrupt, or upon receiving a hardware reset.

In full power-down mode, both the PLL and the clock to the

core are stopped. The on-chip oscillator can be halted or can

continue to oscillate, depending on the state of the oscillator

power-down bit in the PLLCON SFR. The TIC, being driven

directly from the oscillator, can also be enabled during power-

down. All other on-chip peripherals are, however, shut down.

Port pins retain their logic levels in this mode, but the DAC

output goes to a high impedance state (three-state). During full

power-down mode, the part consumes a total of approximately

20 µA. There are five ways of terminating power-down mode:

Asserting the RESET Pin (Pin 15)

Returns to normal mode. All registers are set to their default

state and program execution starts at the reset vector once the

RESET pin is de-asserted.

Cycling Power

All registers are set to their default state and program execution

starts at the reset vector approximately 128 ms later.

Time Interval Counter (TIC) Interrupt

Power-down mode is terminated, and the CPU services the TIC

interrupt. The RETI at the end of the TIC ISR returns the core

to the instruction after the one that enabled power-down.

I2C or SPI Interrupt

Power-down mode is terminated, and the CPU services the

I2C/SPI interrupt. The RETI at the end of the ISR returns the

core to the instruction after the one that enabled power-down.

Note that the I2C/SPI power-down interrupt enable bit (SERIPD)

in the PCON SFR must be set to allow this mode of operation.

INT0 Interrupt

Power-down mode is terminated, and the CPU services the

INT0 interrupt. The RETI at the end of the ISR returns the core

to the instruction after the one that enabled power-down. The

INT0 pin must not be driven low during or within two machine

cycles of the instruction that initiates power-down mode. Note

that the INT0 power-down interrupt enable bit (INT0PD) in

the PCON SFR must be set to allow this mode of operation.

Power-On Reset (POR)

An internal POR is implemented on the ADuC841/ADuC842/

ADuC843.

3 V Part

For DVDD below 2.45 V, the internal POR holds the part in reset.

As DVDD rises above 2.45 V, an internal timer times out for

approximately 128 ms before the part is released from reset. The

user must ensure that the power supply has reached a stable

2.7 V minimum level by this time. Likewise on power-down, the

internal POR holds the part in reset until the power supply has

dropped below 1 V. Figure 82 illustrates the operation of the

internal POR in detail.

128ms TYP 1.0V TYP

128ms TYP

2.45V TYP

1.0V TYP

INTERNAL

CORE RESET

03260-0-082

Figure 82. Internal POR Operation

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 75 of 88

5 V Part

For DVDD below 4.5 V, the internal POR holds the part in reset.

As DVDD rises above 4.5 V, an internal timer times out for

approximately 128 ms before the part is released from reset. The

user must ensure that the power supply has reached a stable

4.75 V minimum level by this time. Likewise on power-down,

the internal POR holds the part in reset until the power supply

has dropped below 1 V. Figure 83 illustrates the operation of the

internal POR in detail.

128ms 1.0V

128ms

4.75V

1.0V TYP

INTERNAL

CORE RESET

03260-0-096

Figure 83. Internal POR Operation

Grounding and Board Layout Recommendations

As with all high resolution data converters, special attention

must be paid to grounding and PC board layout of ADuC841/

ADuC842/ADuC843 based designs to achieve optimum

performance from the ADC and the DACs. Although the parts

have separate pins for analog and digital ground (AGND and

DGND), the user must not tie these to two separate ground

planes unless the two ground planes are connected together

very close to the part, as illustrated in the simplified example of

Figure 84a. In systems where digital and analog ground planes

are connected together somewhere else (for example, at the

system’s power supply), they cannot be connected again near the

part since a ground loop would result. In these cases, tie all the

part’s AGND and DGND pins to the analog ground plane, as

illustrated in Figure 84b. In systems with only one ground plane,

ensure that the digital and analog components are physically

separated onto separate halves of the board such that digital

return currents do not flow near analog circuitry and vice versa.

The part can then be placed between the digital and analog

sections, as illustrated in Figure 84c.

In all of these scenarios, and in more complicated real-life

applications, keep in mind the flow of current from the supplies

and back to ground. Make sure the return paths for all currents

are as close as possible to the paths that the currents took to

reach their destinations. For example, do not power components

on the analog side of Figure 84b with DVDD since that would

force return currents from DVDD to flow through AGND. Also,

try to avoid digital currents flowing under analog circuitry,

which could happen if the user places a noisy digital chip on the

left half of the board in Figure 84c. Whenever possible, avoid

large discontinuities in the ground plane(s) (like those formed

by a long trace on the same layer), since they force return

signals to travel a longer path. And of course, make all connec-

tions to the ground plane directly, with little or no trace

separating the pin from its via to ground.

If the user plans to connect fast logic signals (rise/fall time <

5 ns) to any of the part’s digital inputs, a series resistor should be

added to each relevant line to keep rise and fall times longer

than 5 ns at the part’s input pins. A value of 100 Ω or 200 Ω is

usually sufficient to prevent high speed signals from coupling

capacitively into the part and from affecting the accuracy of

ADC conversions.

DGNDAGND

PLACE ANALOG

COMPONENTS

HERE

PLACE DIGITAL

COMPONENTS

HERE

GND

PLACE ANALOG

COMPONENTS

HERE

PLACE DIGITAL

COMPONENTS

HERE

DGND

AGND

PLACE ANALOG

COMPONENTS

HERE

PLACE DIGITAL

COMPONENTS

HERE

03260-0-083

Figure 84. System Grounding Schemes

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 76 of 88

C1+

V+

C1–

C2+

C2–

V–

T2OUT

R2IN

GND

T1OUT

R1IN

R1OUT

T1IN

T2IN

R2OUT

ADM202

9-PIN D-SUB

FEMALE

47 46 44 43 42 4152 51 50 49 48 45

1kΩDV

1kΩ2-PIN HEADER FOR

EMULATION ACCESS

(NORMALLY OPEN)

DOWNLOAD/DEBUG

ENABLE JUMPER

(NORMALLY OPEN)

11.0592MHz (ADuC841)

32.768kHz (ADuC842/ADuC843)

AGND

REF

DAC0

DAC1

DGND

PSEN

DGND

XTAL2

XTAL1

RESET

RXD

TXD

DGND

NOT CONNECTED IN THIS EXAMPLE

ADuC841/ADuC842/ADuC843

ADC0

ADC7

ANALOG INPUT

VREF OUTPUT

DAC OUTPU

03260-0-084

Figure 85. Example System (PQFP Package), DACs Not Present on ADuC843

OTHER HARDWARE CONSIDERATIONS

To facilitate in-circuit programming, plus in-circuit debug and

emulation options, users will want to implement some simple

connection points in their hardware to allow easy access to

download, debug, and emulation modes.

In-Circuit Serial Download Access

Nearly all ADuC841/ADuC842/ADuC843 designs want to take

advantage of the in-circuit reprogrammability of the chip. This

is accomplished by a connection to the ADuC841/ADuC842/

ADuC843’s UART, which requires an external RS-232 chip for

level translation if downloading code from a PC. Basic configura-

tion of an RS-232 connection is illustrated in Figure 85 with a

simple ADM202 based circuit. If users would rather not design

an RS-232 chip onto a board, refer to Application Note uC006, A

4-Wire UART-to-PC Interface, (at www.analog.com/microconverter)

for a simple (and zero-cost-per-board) method of gaining in-

circuit serial download access to the part.

In addition to the basic UART connections, users also need a

way to trigger the chip into download mode. This is accom-

plished via a 1 kΩ pull-down resistor that can be jumpered onto

the PSEN pin, as shown in Figure 85. To get the part into download

mode, simply connect this jumper and power-cycle the device

(or manually reset the device, if a manual reset button is available),

and it will be ready to serially receive a new program. With the

jumper removed, the device comes up in normal mode (and

runs the program) whenever power is cycled or RESET is toggled.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 77 of 88

Note that PSEN is normally an output (as described in the

External Memory Interface section) and is sampled as an input

only on the falling edge of RESET, i.e., at power-up or upon an

external manual reset. Note also that if any external circuitry

unintentionally pulls PSEN low during power-up or reset

events, it could cause the chip to enter download mode and

therefore fail to begin user code execution as it should. To pre-

vent this, ensure that no external signals are capable of pulling

the PSEN pin low, except for the external PSEN jumper itself.

Embedded Serial Port Debugger

From a hardware perspective, entry into serial port debug mode

is identical to the serial download entry sequence described in

the preceding section. In fact, both serial download and serial

port debug modes can be thought of as essentially one mode of

operation used in two different ways. Note that the serial port

debugger is fully contained on the part (unlike ROM monitor

type debuggers), and therefore no external memory is needed to

enable in-system debug sessions.

Single-Pin Emulation Mode

Also built into the part is a dedicated controller for single-pin

in-circuit emulation (ICE) using standard production ADuC841/

ADuC842/ADuC843 devices. In this mode, emulation access is

gained by connection to a single pin, the EA pin. Normally, this

pin is hardwired either high or low to select execution from

internal or external program memory space, as described

earlier. To enable single-pin emulation mode, however, users

need to pull the EA pin high through a 1 kΩ resistor, as shown

in Figure 85. The emulator then connects to the 2-pin header

also shown in Figure 85. To be compatible with the standard

connector that comes with the single-pin emulator available

from Accutron Limited (www.accutron.com), use a 2-pin

0.1 inch pitch friction lock header from Molex (www.molex.com)

such as their part number 22-27-2021. Be sure to observe the

polarity of this header. As represented in Figure 85, when the

friction lock tab is at the right, the ground pin should be the

lower of the two pins (when viewed from the top).

Typical System Configuration

The typical configuration shown in Figure 85 summarizes some

of the hardware considerations that were discussed in previous

sections.

DEVELOPMENT TOOLS

There are two models of development tools available for the

ADuC841/ADuC842/ADuC843:

• QuickStartTM—Entry-level development system

• QuickStart Plus—Comprehensive development system

These systems are described briefly in the following sections.

QUICKSTART DEVELOPMENT SYSTEM

The QuickStart Development System is an entry-level, low cost

development tool suite supporting the parts. The system

consists of the following PC based (Windows® compatible)

hardware and software development tools.

Hardware Evaluation board and serial port

programming cable.

Software Serial download software.

Miscellaneous CD-ROM documentation and prototype

device.

A brief description of some of the software tools and

components in the QuickStart Development System follows.

Download—In-Circuit Serial Downloader

The serial downloader is a Windows application that allows the

user to serially download an assembled program (Intel® hexadeci-

mal format file) to the on-chip program flash memory via the

serial COM1 port on a standard PC. Application Note uC004

details this serial download protocol and is available from

www.analog.com/microconverter.

ASPIRE—IDE

The ASPIRE integrated development environment is a Windows

application that allows the user to compile, edit, and debug code

in the same environment. The ASPIRE software allows users to

debug code execution on silicon using the MicroConverter

UART serial port. The debugger provides access to all on-chip

peripherals during a typical debug session as well as single step,

animate, and break-point code execution control.

Note that the ASPIRE IDE is also included as part of the

QuickStart Plus System. As part of the QuickStart Plus System,

the ASPIRE IDE also supports mixed level and C source debug.

This is not available in the QuickStart System, but there is an

example project that demonstrates this capability.

QuickStart Plus Development System

The QuickStart Plus Development System offers users enhanced

nonintrusive debug and emulation tools. The system consists of

the following PC based (Windows compatible) hardware and

software development tools.

Hardware Prototype Board. Accutron Nonintrusive

Single-Pin Emulator.

Software ASPIRE Integrated Development

Environment. Features full C and assembly

emulation using the Accutron single pin

emulator.

Miscellaneous CD-ROM documentation.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 78 of 88

TIMING SPECIFICATIONS1, 2, 3

Table 41. AVDD =2.7 V to 3.6 V or 4.75 V to 5.25 V, DVDD = 2.7 V to 3.6 V or 4.75 V to 5.25 V; all specifications TMIN to TMAX,

unless otherwise noted

Parameter 32.768 kHz External Crystal

ADuC842/ADuC843 CLOCK INPUT (External Clock Driven XTAL1) Min Typ Max Unit

tCK XTAL1 Period 30.52 µs

tCKL XTAL1 Width Low 6.26 µs

tCKH XTAL1 Width High 6.26 µs

tCKR XTAL1 Rise Time 9 ns

tCKF XTAL1 Fall Time 9 ns

1/tCORE ADuC842/ADuC843 Core Clock Frequency4 0.131 16.78 MHz

tCORE ADuC842/ADuC843 Core Clock Period5 0.476 µs

tCYC ADuC842/ADuC843 Machine Cycle Time6 0.059 0.476 7.63 µs

1 AC inputs during testing are driven at DVDD – 0.5 V for a Logic 1 and 0.45 V for Logic 0. Timing measurements are made at VIH min for Logic 1 and VIL max for Logic 0, as

shown in Figure 87.

2 For timing purposes, a port pin is no longer floating when a 100 mV change from load voltage occurs. A port pin begins to float when a 100 mV change from the

loaded VOH/VOL level occurs, as shown in Figure 87.

3 CLOAD for all outputs = 80 pF, unless otherwise noted.

4 ADuC842/ADuC843 internal PLL locks onto a multiple (512 times) of the 32.768 kHz external crystal frequency to provide a stable 16.78 MHz internal clock for the

system. The core can operate at this frequency or at a binary submultiple called Core_Clk, selected via the PLLCON SFR.

5 This number is measured at the default Core_Clk operating frequency of 2.09 MHz.

6 ADuC842/ADuC843 machine cycle time is nominally defined as 1/Core_CLK.

Parameter Variable External Crystal

ADuC841 CLOCK INPUT (External Clock Driven XTAL1) Min Typ Max Unit

tCK XTAL1 Period 62.5 1000 ns

tCKL XTAL1 Width Low 20 ns

tCKH XTAL1 Width High 20 ns

tCKR XTAL1 Rise Time 20 ns

tCKF XTAL1 Fall Time 20 ns

1/tCORE ADuC841 Core Clock Frequency 0.131 20 MHz

tCORE ADuC841 Core Clock Period 0.476 µs

tCYC ADuC841 Machine Cycle Time 0.05 0.476 7.63 µs

CKH

CKL

CKF

CKR

03260-0-085

Figure 86. XTAL1 Input

– 0.5V

0.45V

0.2DV

+ 0.9V

TEST POINTS

0.2DV

– 0.1V

LOAD

– 0.1V

LOAD

+ 0.1V

TIMING

REFERENCE

POINTS

LOAD

– 0.1VV

LOAD

– 0.1V

03260-0-086

Figure 87. Timing Waveform Characteristics

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 79 of 88

Parameter 16 MHz Core Clk 8 MHz Core Clock

EXTERNAL DATA MEMORY READ CYCLE Min Max Min Max Unit

tRLRH RD Pulse Width 60 125 ns

tAVLL Address Valid after ALE Low 60 120 ns

tLLAX Address Hold after ALE Low 145 290 ns

tRLDV RD Low to Valid Data In 48 100 Ns

tRHDX Data and Address Hold after RD 0 0 ns

tRHDZ Data Float after RD 150 625 ns

tLLDV ALE Low to Valid Data In 170 350 ns

tAVDV Address to Valid Data In 230 470 ns

tLLWL ALE Low to RD or WR Low 130 255 ns

tAVWL Address Valid to RD or WR Low 190 375 ns

tRLAZ RD Low to Address Float 15 35 ns

tWHLH RD or WR High to ALE High 60 120 ns

03260-0-087

ALE (O)

PORT 0 (I/O)

PORT 2 (O)

WHLH

LLDV

LLWL

RLRH

AVWL

LLAX

AVLL

RLAZ

RHDX

RHDZ

AVDV



A7 (OUT) DATA (IN)

A16



A23 A8 A15

RLDV

PSEN (O)

RD (O)

Figure 88. External Data Memory Read Cycle

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 80 of 88

Parameter 16 MHz Core Clk 8 MHz Core Clock

EXTERNAL DATA MEMORY WRITE CYCLE Min Max Min Max Unit

tWLWH WR Pulse Width 65 130 ns

tAVLL Address Valid after ALE Low 60 120 ns

tLLAX Address Hold after ALE Low 65 135 ns

tLLWL ALE Low to RD or WR Low 130 260 ns

tAVWL Address Valid to RD or WR Low 190 375 ns

tQVWX Data Valid to WR Transition 60 120 ns

tQVWH Data Setup before WR 120 250 ns

tWHQX Data and Address Hold after WR 380 755 ns

tWHLH RD or WR High to ALE High 60 125 ns

03260-0-088

ALE (O)

PORT 2 (O)

tWHLH

tWLWH

tLLWL

tAVWL

tLLAX

tAVLL

tQVWX

tQVWH

tWHQX



A7 DATA

A16



A23 V8 A15

PSEN (O)

WR (O)

Figure 89. External Data Memory Write Cycle

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 81 of 88

Parameter

I2C COMPATIBLE INTERFACE TIMING Min Max Unit

tL SCLOCK Low Pulse Width 1.3 µs

tH SCLOCK High Pulse Width 0.6 µs

tSHD Start Condition Hold Time 0.6 µs

tDSU Data Setup Time 100 µs

tDHD Data Hold Time 0.9 µs

tRSU Setup Time for Repeated Start 0.6 µs

tPSU Stop Condition Setup Time 0.6 µs

tBUF Bus Free Time between a Stop Conditionand a Start Condition 1.3 µs

tR Rise Time of Both SCLOCK and SDATA 300 ns

tF Fall Time of Both SCLOCK and SDATA 300 ns

tSUP1 Pulse Width of Spike Suppressed 50 ns

1Input filtering on both the SCLOCK and SDATA inputs suppresses noise spikes less than 50 ns.

MSB

BUF

SDATA (I/O)

SCLK (I)

STOP

CONDITION START

CONDITION REPEATED

START

LSB ACK MSB

1 2-7 8 9 1

S(R)

PSU

DSU

SHD

DHD

SUP

DSU

DHD

SUP

RSU

03260-0-091

Figure 90. I2C Compatible Interface Timing

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 82 of 88

Parameter

SPI MASTER MODE TIMING (CPHA = 1) Min Typ Max Unit

tSL SCLOCK Low Pulse Width1 476 ns

tSH SCLOCK High Pulse Width1 476 ns

tDAV Data Output Valid after SCLOCK Edge 50 ns

tDSU Data Input Setup Time before SCLOCK Edge 100 ns

tDHD Data Input Hold Time after SCLOCK Edge 100 ns

tDF Data Output Fall Time 10 25 ns

tDR Data Output Rise Time 10 25 ns

tSR SCLOCK Rise Time 10 25 ns

tSF SCLOCK Fall Time 10 25 ns

1 Characterized under the following conditions:

a. Core clock divider bits CD2, CD1, and CD0 bits in PLLCON SFR set to 0, 1, and 1, respectively, i.e., core clock frequency = 2.09 MHz.

b. SPI bit-rate selection bits SPR1 and SPR0 in SPICON SFR set to 0 and 0, respectively.

SCLOCK

(CPOL = 0)

DSU

SCLOCK

(CPOL = 1)

MOSI

MISO

MSB LSB

LSB IN

BITS 6–1

DHD

DAV

MSB IN

03260-0-092

Figure 91. SPI Master Mode Timing (CPHA = 1)

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 83 of 88

Parameter

SPI MASTER MODE TIMING (CPHA = 0) Min Typ Max Unit

tSL SCLOCK Low Pulse Width1 476 ns

tSH SCLOCK High Pulse Width1 476 ns

tDAV Data Output Valid after SCLOCK Edge 50 ns

tDOSU Data Output Setup before SCLOCK Edge 150 ns

tDSU Data Input Setup Time before SCLOCK Edge 100 ns

tDHD Data Input Hold Time after SCLOCK Edge 100 ns

tDF Data Output Fall Time 10 25 ns

tDR Data Output Rise Time 10 25 ns

tSR SCLOCK Rise Time 10 25 ns

tSF SCLOCK Fall Time 10 25 ns

1 Characterized under the following conditions:

a. Core clock divider bits CD2, CD1, and CD0 bits in PLLCON SFR set to 0, 1, and 1, respectively, i.e., core clock frequency = 2.09 MHz.

b. SPI bit-rate selection bits SPR1 and SPR0 in SPICON SFR set to 0 and 0, respectively.

SCLOCK

(CPOL = 0)

DSU

SCLOCK

(CPOL = 1)

MOSI

MISO

MSB LSB

LSB IN

BITS 6–1

DHD

DAV

DOSU

MSB IN

03260-0-093

Figure 92. SPI Master Mode Timing (CPHA = 0)

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 84 of 88

Parameter

SPI SLAVE MODE TIMING (CPHA = 1) Min Typ Max Unit

tSS SS to SCLOCK Edge 0 ns

tSL SCLOCK Low Pulse Width 330 ns

tSH SCLOCK High Pulse Width 330 ns

tDAV Data Output Valid after SCLOCK Edge 50 ns

tDSU Data Input Setup Time before SCLOCK Edge 100 ns

tDHD Data Input Hold Time after SCLOCK Edge 100 ns

tDF Data Output Fall Time 10 25 ns

tDR Data Output Rise Time 10 25 ns

tSR SCLOCK Rise Time 10 25 ns

tSF SCLOCK Fall Time 10 25 ns

tSFS SS High after SCLOCK Edge 0 ns

MISO

MOSI

SCLOCK

(CPOL = 1)

SCLOCK

(CPOL = 0)

MSB BITS 6–1 LSB

BITS 6–1 LSB IN

DHD

DSU

DAV

SFS

MSB IN

03260-0-094

Figure 93. SPI Slave Mode Timing (CPHA = 1)

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 85 of 88

Parameter

SPI SLAVE MODE TIMING (CPHA = 0) Min Typ Max Unit

tSS SS to SCLOCK Edge 0 ns

tSL SCLOCK Low Pulse Width 330 ns

tSH SCLOCK High Pulse Width 330 ns

tDAV Data Output Valid after SCLOCK Edge 50 ns

tDSU Data Input Setup Time before SCLOCK Edge 100 ns

tDHD Data Input Hold Time after SCLOCK Edge 100 ns

tDF Data Output Fall Time 10 25 ns

tDR Data Output Rise Time 10 25 ns

tSR SCLOCK Rise Time 10 25 ns

tSF SCLOCK Fall Time 10 25 ns

tDOSS Data Output Valid after SS Edge 20 ns

tSFS SS High after SCLOCK Edge ns

MISO

MOSI

SCLOCK

(CPOL = 1)

SCLOCK

(CPOL = 0)

MSB BITS 6–1 LSB

BITS 6–1 LSB IN

DHD

DSU

DAV

DOSS

SFS

MSB IN

03260-0-095

Figure 94. SPI Slave Mode Timing (CPHA = 0)

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 86 of 88

OUTLINE DIMENSIONS

SEATING

PLANE

VIEW A

0.23

0.11

2.45

MAX

1.03

0.88

0.73

TOP VIEW

(PINS DOWN)

PIN 1

0.65 BSC

14.15

13.90 SQ

13.65

7.80

REF 10.20

10.00 SQ

9.80

0.38

0.22

VIEW A

ROTATED 90° CCW

7°

0°

2.10

2.00

1.95 0.13 MIN

COPLANARITY

COMPLIANT TO JEDEC STANDARDS MO-112-AC-1

Figure 95. 52-Lead Plastic Quad Flatpack [MQFP]

(S-52)

Dimensions shown in millimeters

PIN 1

INDICATOR

TOP

VIEW

7.75

BSC SQ

8.00

BSC SQ

BOTTOM

VIEW

6.25

6.10

5.95

0.50

0.40

0.30

0.23

0.18

0.50 BSC 0.20 REF



12° MAX 0.80 MAX

0.65 TYP

1.00

0.85

0.80

6.50

REF

SEATING

PLANE

0.60 MAX

0.60 MAX PIN 1

INDICATOR

COPLANARITY

0.08

0.05 MAX

0.02 NOM

0.25MIN

COMPLIANT TO JEDEC STANDARDS MO-220-VLLD-2

Figure 96. 56-Lead Frame Chip Scale Package [LFCSP]

8 mm × 8 mm Body (CP-56)

Dimensions shown in millimeters

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 87 of 88

ORDERING GUIDES

Table 42. ADuC841 Ordering Guide

Model

Supply Voltage

VDD

User Program

Code Space

Temperature

Range

Package Description

Package

Option

ADuC841BS62-5 5 62 –40°C to +85°C 52-Lead Plastic Quad Flatpack S-52

ADuC841BS62-3 3 62 –40°C to +85°C 52-Lead Plastic Quad Flatpack S-52

ADuC841BCP62-5 5 62 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC841BCP62-3 3 62 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC841BCP8-5 5 8 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC841BCP8-3 3 8 –40°C to +85°C 56-Lead Chip Scale Package CP-56

EVAL-ADuC841QS 5 QuickStart Development System

EVAL-ADuC841QSP2 5 QuickStart Plus Development System

Table 43. ADuC842 Ordering Guide

Model

Supply Voltage

VDD

User Program

Code Space

Temperature

Range

Package Description

Package

Option

ADuC842BS62-5 5 62 –40°C to +85°C 52-Lead Plastic Quad Flatpack S-52

ADuC842BS62-3 3 62 –40°C to +85°C 52-Lead Plastic Quad Flatpack S-52

ADuC842BCP62-5 5 62 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC842BCP62-3 3 62 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC842BCP32-5 5 32 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC842BCP32-3 3 32 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC842BCP8-5 5 8 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC842BCP8-3 3 8 –40°C to +85°C 56-Lead Chip Scale Package CP-56

EVAL-ADuC842QS 5 QuickStart Development System

EVAL-ADuC842QSP2 5 QuickStart Plus Development System

Table 44. ADuC843 Ordering Guide

Model

Supply Voltage

VDD

User Program

Code Space

Temperature

Range

Package Description

Package

Option

ADuC843BS62-5 5 62 –40°C to +85°C 52-Lead Plastic Quad Flatpack S-52

ADuC843BS62-3 3 62 –40°C to +85°C 52-Lead Plastic Quad Flatpack S-52

ADuC843BCP62-5 5 62 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC843BCP62-3 3 62 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC843BCP32-5 5 32 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC843BCP32-3 3 32 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC843BCP8-5 5 8 –40°C to +85°C 56-Lead Chip Scale Package CP-56

ADuC843BCP8-3 3 8 –40°C to +85°C 56-Lead Chip Scale Package CP-56

EVAL-ADuC842QS1 5 QuickStart Development System

EVAL-ADuC842QSP1, 2 5 QuickStart Plus Development System

1The only difference between the ADuC842 and ADuC843 parts is the voltage output DACs on the ADuC842; thus the evaluation system for the ADuC842 is also

suitable for the ADuC843.

2The Quickstart Plus system can only be ordered directly from Accutron. It can be purchased from the website www.accutron.com.

ADuC841/ADuC842/ADuC843

Rev. 0 | Page 88 of 88

Notes

Purchase of licensed I2C components of Analog Devices or one of its sublicensed Associated Companies conveys a license for the purchaser under the Philips I2C Patent

Rights to use these components in an I2C system, provided that the system conforms to the I2C Standard Specification as defined by Philips.

registered trademarks are the property of their respective owners.

C03260-0-11/03(0)